TNY274-280 Datasheet by Power Integrations

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TNY274-280
TinySwitch-III Family
www.powerint.com January 2009
Energy-Effi cient, Off-Line Switcher With
Enhanced Flexibility and Extended Power Range
®
Output Power Table
Product3
230 VAC ± 15% 85-265 VAC
Adapter1
Peak or
Open
Frame2
Adapter1
Peak or
Open
Frame2
TNY274P/G 6 W 11 W 5 W 8.5 W
TNY275P/G 8.5 W 15 W 6 W 11.5 W
TNY276P/G 10 W 19 W 7 W 15 W
TNY277P/G 13 W 23.5 W 8 W 18 W
TNY278P/G 16 W 28 W 10 W 21.5 W
TNY279P/G 18 W 32 W 12 W 25 W
TNY280P/G 20 W 36.5 W 14 W 28.5 W
Table 1. Output Power Table.
Notes:
1. Minimum continuous power in a typical non-ventilated enclosed adapter
measured at +50 °C ambient. Use of an external heatsink will increase power
capability.
2. Minimum peak power capability in any design or minimum continuous power in
an open frame design (see Key Applications Considerations).
3. Packages: P: DIP-8C, G: SMD-8C. See Part Ordering Information.
Product Highlights
Lowest System Cost with Enhanced Flexibility
Simple ON/OFF control, no loop compensation needed
Selectable current limit through BP/M capacitor value
Higher current limit extends peak power or, in open
frame applications, maximum continuous power
Lower current limit improves effi ciency in enclosed
adapters/chargers
Allows optimum TinySwitch-III choice by swapping
devices with no other circuit redesign
Tight I2f parameter tolerance reduces system cost
Maximizes MOSFET and magnetics power delivery
Minimizes max overload power, reducing cost of
transformer, primary clamp & secondary components
ON-time extension – extends low line regulation range/hold-up
time to reduce input bulk capacitance
Self-biased: no bias winding or bias components
Frequency jittering reduces EMI fi lter costs
Pin-out simplifi es heatsinking to the PCB
SOURCE pins are electrically quiet for low EMI
Enhanced Safety and Reliability Features
Accurate hysteretic thermal shutdown protection with
automatic recovery eliminates need for manual reset
Improved auto-restart delivers <3% of maximum power in short
circuit and open loop fault conditions
Output overvoltage shutdown with optional Zener
Line undervoltage detect threshold set using a single optional
resistor
Very low component count enhances reliability and enables
single-sided printed circuit board layout
High bandwidth provides fast turn on with no overshoot and
excellent transient load response
Extended creepage between DRAIN and all other pins improves
eld reliability
EcoSmart®– Extremely Energy Ef cient
Easily meets all global energy effi ciency regulations
No-load <150 mW at 265 VAC without bias winding, <50 mW
with bias winding
ON/OFF control provides constant effi ciency down to very light
loads – ideal for mandatory CEC regulations and 1 W PC
standby requirements
Applications
Chargers/adapters for cell/cordless phones, PDAs, digital
cameras, MP3/portable audio, shavers, etc.
PC Standby and other auxiliary supplies
DVD/PVR and other low power set top decoders
Supplies for appliances, industrial systems, metering, etc.
Description
TinySwitch-III incorporates a 700 V power MOSFET, oscillator,
high voltage switched current source, current limit (user
selectable) and thermal shutdown circuitry. The IC family uses an
ON/OFF control scheme and offers a design fl exible solution with
a low system cost and extended power capability.
Figure 1. Typical Standby Application.
PI-4095-082205
Wide-Range
HV DC Input D
S
EN/UV
BP/M
+
-
+
-
DC
Output
TinySwitch-III
EDIE EEE l8 1R3 3+0 HFAE $8 Efigflfi'fi ‘
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TNY274-280
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Pin Functional Description
DRAIN (D) Pin:
This pin is the power MOSFET drain connection. It provides
internal operating current for both startup and steady-state
operation.
BYPASS/MULTI-FUNCTION (BP/M) Pin:
This pin has multiple functions:
It is the connection point for an external bypass capacitor for
the internally generated 5.85 V supply.
It is a mode selector for the current limit value, depending on
the value of the capacitance added. Use of a 0.1 μF
capacitor results in the standard current limit value. Use of a
1 μF capacitor results in the current limit being reduced to
that of the next smaller device size. Use of a 10 μF capacitor
results in the current limit being increased to that of the next
larger device size for TNY275-280.
It provides a shutdown function. When the current into the
bypass pin exceeds ISD, the device latches off until the
BP/M voltage drops below 4.9 V, during a power down. This
can be used to provide an output overvoltage function with a
Zener connected from the BP/M pin to a bias winding supply.
1.
2.
3.
ENABLE/UNDERVOLTAGE (EN/UV) Pin:
This pin has dual functions: enable input and line undervoltage
sense. During normal operation, switching of the power
MOSFET is controlled by this pin. MOSFET switching is
terminated when a current greater than a threshold current is
drawn from this pin. Switching resumes when the current being
Figure 2. Functional Block Diagram.
PI-4077-062306
CLOCK
OSCILLATOR
5.85 V
4.9 V
SOURCE
(S)
S
R
Q
DCMAX
BYPASS/
MULTI-FUNCTION
(BP/M)
+
-
V
ILIMIT
FAULT
PRESENT
CURRENT LIMIT
COMPARATOR
ENABLE
LEADING
EDGE
BLANKING
THERMAL
SHUTDOWN
+
-
DRAIN
(D)
REGULATOR
5.85 V
BYPASS PIN
UNDER-VOLTAGE
1.0 V + V
T
ENABLE/
UNDER-
VOLTAGE
(EN/UV)
Q
115 μA 25 μA
LINE UNDER-VOLTAGE
RESET
AUTO-
RESTART
COUNTER
JITTER
1.0 V
6.4 V
BYPASS
CAPACITOR
SELECT AND
CURRENT
LIMIT STATE
MACHINE
OVP
LATCH
Figure 3. Pin Confi guration.
PI-4078-080905
DS
BP/M S
S
EN/UV
P Package (DIP-8C)
G Package (SMD-8C)
8
5
7
1
4
2
S
6
EPOWER ‘ nus-"mu
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pulled from the pin drops to less than a threshold current. A
modulation of the threshold current reduces group pulsing. The
threshold current is between 75 μA and 115 μA.
The EN/UV pin also senses line undervoltage conditions through
an external resistor connected to the DC line voltage. If there is
no external resistor connected to this pin, TinySwitch-III detects
its absence and disables the line undervoltage function.
SOURCE (S) Pin:
This pin is internally connected to the output MOSFET source for
high voltage power return and control circuit common.
TinySwitch-III Functional Description
TinySwitch-III combines a high voltage power MOSFET switch
with a power supply controller in one device. Unlike conventional
PWM (pulse width modulator) controllers, it uses a simple
ON/OFF control to regulate the output voltage.
The controller consists of an oscillator, enable circuit (sense and
logic), current limit state machine, 5.85 V regulator, BYPASS/
MULTI-FUNCTION pin undervoltage, overvoltage circuit, and
current limit selection circuitry, over-temperature protection,
current limit circuit, leading edge blanking, and a 700 V power
MOSFET. TinySwitch-III incorporates additional circuitry for line
undervoltage sense, auto-restart, adaptive switching cycle on-
time extension, and frequency jitter. Figure 2 shows the
functional block diagram with the most important features.
Oscillator
The typical oscillator frequency is internally set to an average of
132 kHz. Two signals are generated from the oscillator: the
maximum duty cycle signal (DCMAX) and the clock signal that
indicates the beginning of each cycle.
The oscillator incorporates circuitry that introduces a small
amount of frequency jitter, typically 8 kHz peak-to-peak, to
minimize EMI emission. The modulation rate of the frequency
jitter is set to 1 kHz to optimize EMI reduction for both average
and quasi-peak emissions. The frequency jitter should be
measured with the oscilloscope triggered at the falling edge of
the DRAIN waveform. The waveform in Figure 4 illustrates the
frequency jitter.
Enable Input and Current Limit State Machine
The enable input circuit at the EN/UV pin consists of a low
impedance source follower output set at 1.2 V. The current
through the source follower is limited to 115 μA. When the
current out of this pin exceeds the threshold current, a low logic
level (disable) is generated at the output of the enable circuit,
until the current out of this pin is reduced to less than the
threshold current. This enable circuit output is sampled at the
beginning of each cycle on the rising edge of the clock signal. If
high, the power MOSFET is turned on for that cycle (enabled). If
low, the power MOSFET remains off (disabled). Since the
sampling is done only at the beginning of each cycle,
subsequent changes in the EN/UV pin voltage or current during
the remainder of the cycle are ignored.
The current limit state machine reduces the current limit by
discrete amounts at light loads when TinySwitch-III is likely to
switch in the audible frequency range. The lower current limit
raises the effective switching frequency above the audio range
and reduces the transformer fl ux density, including the
associated audible noise. The state machine monitors the
sequence of enable events to determine the load condition and
adjusts the current limit level accordingly in discrete amounts.
Under most operating conditions (except when close to no-
load), the low impedance of the source follower keeps the
voltage on the EN/UV pin from going much below 1.2 V in the
disabled state. This improves the response time of the
optocoupler that is usually connected to this pin.
5.85 V Regulator and 6.4 V Shunt Voltage Clamp
The 5.85 V regulator charges the bypass capacitor connected
to the BYPASS pin to 5.85 V by drawing a current from the
voltage on the DRAIN pin whenever the MOSFET is off. The
BYPASS/MULTI-FUNCTION pin is the internal supply voltage
node. When the MOSFET is on, the device operates from the
energy stored in the bypass capacitor. Extremely low power
consumption of the internal circuitry allows TinySwitch-III to
operate continuously from current it takes from the DRAIN pin.
A bypass capacitor value of 0.1 μF is suf cient for both high
frequency decoupling and energy storage.
In addition, there is a 6.4 V shunt regulator clamping the
BYPASS/MULTI-FUNCTION pin at 6.4 V when current is
provided to the BYPASS/MULTI-FUNCTION pin through an
external resistor. This facilitates powering of TinySwitch-III
externally through a bias winding to decrease the no-load
consumption to well below 50 mW.
BYPASS/MULTI-FUNCTION Pin Undervoltage
The BYPASS/MULTI-FUNCTION pin undervoltage circuitry
disables the power MOSFET when the BYPASS/MULTI-
FUNCTION pin voltage drops below 4.9 V in steady state
operation. Once the BYPASS/MULTI-FUNCTION pin voltage
drops below 4.9 V in steady state operation, it must rise back to
5.85 V to enable (turn-on) the power MOSFET.
Figure 4. Frequency Jitter.
600
0510
136 kHz
128 kHz
VDRAIN
Time (μs)
PI-2741-041901
500
400
300
200
100
0
v DRAIN DC-OUTPUT EWWFF A
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TNY274-280
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Over Temperature Protection
The thermal shutdown circuitry senses the die temperature.
The threshold is typically set at 142 °C with 75 °C hysteresis.
When the die temperature rises above this threshold the power
MOSFET is disabled and remains disabled until the die
temperature falls by 75 °C, at which point it is re-enabled. A
large hysteresis of 75 °C (typical) is provided to prevent over-
heating of the PC board due to a continuous fault condition.
Current Limit
The current limit circuit senses the current in the power
MOSFET. When this current exceeds the internal threshold
(ILIMIT), the power MOSFET is turned off for the remainder of that
cycle. The current limit state machine reduces the current limit
threshold by discrete amounts under medium and light loads.
The leading edge blanking circuit inhibits the current limit
comparator for a short time (tLEB) after the power MOSFET is
turned on. This leading edge blanking time has been set so that
current spikes caused by capacitance and secondary-side
rectifi er reverse recovery time will not cause premature
termination of the switching pulse.
Auto-Restart
In the event of a fault condition such as output overload, output
short circuit, or an open loop condition, TinySwitch-III enters
into auto-restart operation. An internal counter clocked by the
oscillator is reset every time the EN/UV pin is pulled low. If the
EN/UV pin is not pulled low for 64 ms, the power MOSFET
switching is normally disabled for 2.5 seconds (except in the
case of line undervoltage condition, in which case it is disabled
until the condition is removed). The auto-restart alternately
enables and disables the switching of the power MOSFET until
the fault condition is removed. Figure 5 illustrates auto-restart
circuit operation in the presence of an output short circuit.
In the event of a line undervoltage condition, the switching of
the power MOSFET is disabled beyond its normal 2.5 seconds
until the line undervoltage condition ends.
Adaptive Switching Cycle On-Time Extension
Adaptive switching cycle on-time extension keeps the cycle on
until current limit is reached, instead of prematurely terminating
after the DCMAX signal goes low. This feature reduces the
minimum input voltage required to maintain regulation,
extending hold-up time and minimizing the size of bulk
capacitor required. The on-time extension is disabled during the
startup of the power supply, until the power supply output
reaches regulation.
Line Undervoltage Sense Circuit
The DC line voltage can be monitored by connecting an
external resistor from the DC line to the EN/UV pin. During
power up or when the switching of the power MOSFET is
disabled in auto-restart, the current into the EN/UV pin must
exceed 25 μA to initiate switching of the power MOSFET. During
power up, this is accomplished by holding the BYPASS/MULTI-
FUNCTION pin to 4.9 V while the line undervoltage condition
exists. The BYPASS/MULTI-FUNCTION pin then rises from
4.9 V to 5.85 V when the line undervoltage condition goes
away. When the switching of the power MOSFET is disabled in
auto-restart mode and a line undervoltage condition exists, the
auto-restart counter is stopped. This stretches the disable time
beyond its normal 2.5 seconds until the line undervoltage
condition ends.
The line undervoltage circuit also detects when there is no
external resistor connected to the EN/UV pin (less than ~2 μA
into the pin). In this case the line undervoltage function is
disabled.
TinySwitch-III Operation
TinySwitch-III devices operate in the current limit mode. When
enabled, the oscillator turns the power MOSFET on at the
beginning of each cycle. The MOSFET is turned off when the
current ramps up to the current limit or when the DCMAX limit is
reached. Since the highest current limit level and frequency of a
TinySwitch-III design are constant, the power delivered to the
load is proportional to the primary inductance of the transformer
and peak primary current squared. Hence, designing the supply
involves calculating the primary inductance of the transformer
for the maximum output power required. If the TinySwitch-III is
appropriately chosen for the power level, the current in the
calculated inductance will ramp up to current limit before the
DCMAX limit is reached.
Enable Function
TinySwitch-III senses the EN/UV pin to determine whether or
not to proceed with the next switching cycle. The sequence of
cycles is used to determine the current limit. Once a cycle is
started, it always completes the cycle (even when the EN/UV
pin changes state half way through the cycle). This operation
results in a power supply in which the output voltage ripple is
determined by the output capacitor, amount of energy per
switch cycle and the delay of the feedback.
The EN/UV pin signal is generated on the secondary by
comparing the power supply output voltage with a reference
voltage. The EN/UV pin signal is high when the power supply
output voltage is less than the reference voltage.
Figure 5. Auto-Restart Operation.
PI-4098-082305
02500 5000
Time (ms)
0
5
0
10
100
200
300
VDRAIN
VDC-OUTPUT
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TNY274-280
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In a typical implementation, the EN/UV pin is driven by an
optocoupler. The collector of the optocoupler transistor is
connected to the EN/UV pin and the emitter is connected to the
SOURCE pin. The optocoupler LED is connected in series with
a Zener diode across the DC output voltage to be regulated.
When the output voltage exceeds the target regulation voltage
level (optocoupler LED voltage drop plus Zener voltage), the
optocoupler LED will start to conduct, pulling the EN/UV pin
low. The Zener diode can be replaced by a TL431 reference
circuit for improved accuracy.
ON/OFF Operation with Current Limit State Machine
The internal clock of the TinySwitch-III runs all the time. At the
beginning of each clock cycle, it samples the EN/UV pin to
decide whether or not to implement a switch cycle, and based
on the sequence of samples over multiple cycles, it determines
the appropriate current limit. At high loads, the state machine
sets the current limit to its highest value. At lighter loads, the
state machine sets the current limit to reduced values.
V
DRAIN
V
EN
CLOCK
DC
DRAIN
I
MAX
PI-2749-082305
Figure 6. Operation at Near Maximum Loading.
V
DRAIN
V
EN
CLOCK
DC
DRAIN
I
MAX
PI-2667-082305
Figure 7. Operation at Moderately Heavy Loading.
Figure 8. Operation at Medium Loading.
PI-2377-082305
V
DRAIN
V
EN
CLOCK
DC
DRAIN
I
MAX
PI-2661-082305
V
DRAIN
V
EN
CLOCK
DC
DRAIN
I
MAX
Figure 9. Operation at Very Light Load.
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TNY274-280
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Figure 12. Normal Power Down Timing (without UV). Figure 13. Slow Power Down Timing with Optional External (4 MΩ) UV Resistor
Connected to EN/UV Pin.
Figure 10. Power Up with Optional External UV Resistor (4 MΩ)
Connected to EN/UV Pin.
Figure 11. Power Up Without Optional External UV Resistor
Connected to EN/UV Pin.
PI-2395-030801
02.5 5
Time (s)
0
100
200
400
300
0
100
200
VDC-INPUT
VDRAIN
012
Time (ms)
0
200
400
5
0
10
0
100
200
PI-2383-030801
VDC-INPUT
VBYPASS
VDRAIN
PI-2381-1030801
012
Time (ms)
0
200
400
5
0
10
0
100
200
VDC-INPUT
VBYPASS
VDRAIN
PI-2348-030801
0.5 1
Time (s)
0
100
200
300
0
100
200
400
VDC-INPUT
VDRAIN
At near maximum load, TinySwitch-III will conduct during nearly
all of its clock cycles (Figure 6). At slightly lower load, it will
“skip” additional cycles in order to maintain voltage regulation at
the power supply output (Figure 7). At medium loads, cycles
will be skipped and the current limit will be reduced (Figure 8).
At very light loads, the current limit will be reduced even further
(Figure 9). Only a small percentage of cycles will occur to satisfy
the power consumption of the power supply.
The response time of the ON/OFF control scheme is very fast
compared to PWM control. This provides tight regulation and
excellent transient response.
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Power Up/Down
The TinySwitch-III requires only a 0.1 μF capacitor on the
BYPASS/MULTI-FUNCTION pin to operate with standard
current limit. Because of its small size, the time to charge this
capacitor is kept to an absolute minimum, typically 0.6 ms. The
time to charge will vary in proportion to the BYPASS/MULTI-
FUNCTION pin capacitor value when selecting different current
limits. Due to the high bandwidth of the ON/OFF feedback,
there is no overshoot at the power supply output. When an
external resistor (4 MΩ) is connected from the positive DC input
to the EN/UV pin, the power MOSFET switching will be delayed
during power up until the DC line voltage exceeds the threshold
(100 V). Figures 10 and 11 show the power up timing waveform
in applications with and without an external resistor (4 MΩ)
connected to the EN/UV pin.
Under startup and overload conditions, when the conduction
time is less than 400 ns, the device reduces the switching
frequency to maintain control of the peak drain current.
During power down, when an external resistor is used, the
power MOSFET will switch for 64 ms after the output loses
regulation. The power MOSFET will then remain off without any
glitches since the undervoltage function prohibits restart when
the line voltage is low.
Figure 12 illustrates a typical power down timing waveform.
Figure 13 illustrates a very slow power down timing waveform
as in standby applications. The external resistor (4 MΩ) is
connected to the EN/UV pin in this case to prevent unwanted
restarts.
No bias winding is needed to provide power to the chip
because it draws the power directly from the DRAIN pin (see
Functional Description). This has two main benefi ts. First, for a
nominal application, this eliminates the cost of a bias winding
and associated components. Secondly, for battery charger
applications, the current-voltage characteristic often allows the
output voltage to fall close to zero volts while still delivering
power. TinySwitch-III accomplishes this without a forward bias
winding and its many associated components. For applications
that require very low no-load power consumption (50 mW), a
resistor from a bias winding to the BYPASS/MULTI-FUNCTION
pin can provide the power to the chip. The minimum
recommended current supplied is 1 mA. The BYPASS/MULTI-
FUNCTION pin in this case will be clamped at 6.4 V. This
method will eliminate the power draw from the DRAIN pin,
thereby reducing the no-load power consumption and
improving full-load ef ciency.
Current Limit Operation
Each switching cycle is terminated when the DRAIN current
reaches the current limit of the device. Current limit operation
provides good line ripple rejection and relatively constant power
delivery independent of input voltage.
BYPASS/MULTI-FUNCTION Pin Capacitor
The BYPASS/MULTI-FUNCTION pin can use a ceramic
capacitor as small as 0.1 μF for decoupling the internal power
supply of the device. A larger capacitor size can be used to
adjust the current limit. For TNY275-280, a 1 μF BP/M pin
capacitor will select a lower current limit equal to the standard
current limit of the next smaller device and a 10 μF BP/M pin
capacitor will select a higher current limit equal to the standard
current limit of the next larger device. The higher current limit
level of the TNY280 is set to 850 mA typical. The TNY274
MOSFET does not have the capability for increased current limit
so this feature is not available in this device.
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TNY274-280
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Applications Example
The circuit shown in Figure 14 is a low cost, high ef ciency,
yback power supply designed for 12 V, 1 A output from
universal input using the TNY278.
The supply features undervoltage lockout, primary sensed
output overvoltage latching shutdown protection, high
ef ciency (>80%), and very low no-load consumption (<50 mW
at 265 VAC). Output regulation is accomplished using a simple
zener reference and optocoupler feedback.
The recti ed and fi ltered input voltage is applied to the primary
winding of T1. The other side of the transformer primary is
driven by the integrated MOSFET in U1. Diode D5, C2, R1, R2,
and VR1 comprise the clamp circuit, limiting the leakage
inductance turn-off voltage spike on the DRAIN pin to a safe
value. The use of a combination a Zener clamp and parallel RC
optimizes both EMI and energy ef ciency. Resistor R2 allows
the use of a slow recovery, low cost, rectifi er diode by limiting
the reverse current through D5. The selection of a slow diode
also improves ef ciency and conducted EMI but should be a
glass passivated type, with a specifi ed recovery time of 2 μs.
The output voltage is regulated by the Zener diode VR3. When
the output voltage exceeds the sum of the Zener and opto-
coupler LED forward drop, current will fl ow in the optocoupler
LED. This will cause the transistor of the optocoupler to sink
current.When this current exceeds the ENABLE pin threshold
current the next switching cycle is inhibited. When the output
voltage falls below the feedback threshold, a conduction cycle
is allowed to occur and, by adjusting the number of enabled
cycles, output regulation is maintained. As the load reduces,
the number of enabled cycles decreases, lowering the effective
switching frequency and scaling switching losses with load.
This provides almost constant ef ciency down to very light
loads, ideal for meeting energy ef ciency requirements.
As the TinySwitch-III devices are completely self-powered, there
is no requirement for an auxiliary or bias winding on the
transformer. However by adding a bias winding, the output
overvoltage protection feature can be confi gured, protecting the
load against open feedback loop faults.
When an overvoltage condition occurs, such that bias voltage
exceeds the sum of VR2 and the BYPASS/MULTIFUNCTION
(BP/M) pin voltage (28 V+5.85 V), current begins to fl ow into the
BP/M pin. When this current exceeds ISD the internal latching
shutdown circuit in TinySwitch-III is activated. This condition is
reset when the BP/M pin voltage drops below 2.6 V after
removal of the AC input. In the example shown, on opening the
loop, the OVP trips at an output of 17 V.
For lower no-load input power consumption, the bias winding
may also be used to supply the TinySwitch-III device. Resistor
R8 feeds current into the BP/M pin, inhibiting the internal high
voltage current source that normally maintains the BP/M pin
capacitor voltage (C7) during the internal MOSFET off time.
This reduces the no-load consumption of this design from
140 mW to 40 mW at 265 VAC.
Figure 14. TNY278P, 12 V, 1 A Universal Input Power Supply.
D
S
S BP/M
EN/UV
L1
1 mH
D1
1N4007
RV1
275 VAC
F1
3.15 A
D2
1N4007
C1
6.8 μF
400 V
C6
1 μF
60 V
C2
22 μF
400 V
C10
1000 μF
25 V
C5
2.2 nF
250 VAC
C11
100 μF
25 V
12 V, 1 A
85 - 265
VAC
RTN
C7
100 nF
50 V
U1
TNY278PN
C4
10 nF
1 kV
VR1
P6KE150A
NC
8
6
4
T1
2
5
1
3
D5
1N4007GP
D6
UF4003
D7
BYV28-200
U2
PC817A
VR2
1N5255B
28 V
VR3
BZX79-C11
11 V
C7 is used to adjust U1
current limit. See circuit
description
*R5 and R8 are optional
components
R5*
3.6 MΩ
R3
47 Ω
1/8 W
R4
2 kΩ
1/8 W
R6
390 Ω
1/8 W
R7
20 Ω
R8*
21 kΩ
1%
R1
1 kΩ
R2
100 Ω
D3
1N4007
D4
1N4007
L2
Ferrite Bead
3.5 × 7.6 mm
PI-4244-111708
TinySwitch-III
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www.powerint.com
Peak Output Power Table
Product
230 VAC ± 15% 85-265 VAC
ILIMIT
-1 ILIMIT ILIMIT+1 ILIMIT
-1 ILIMIT ILIMIT+1
TNY274P/G 8 W 10.9 W 9.1 W 7.1 W 8.5 W 7.1 W
TNY275P/G 10.8 W 12 W 15.1 W 8.4 W 9.3 W 11.8 W
TNY276P/G 11.8 W 15.3 W 19.4 W 9.2 W 11.9 W 15.1 W
TNY277P/G 15.1 W 19.6 W 23.7 W 11.8 W 15.3 W 18.5 W
TNY278P/G 19.4 W 24 W 28 W 15.1 W 18.6 W 21.8 W
TNY279P/G 23.7 W 28.4 W 32.2 W 18.5 W 22 W 25.2 W
TNY280P/G 28 W 32.7 W 36.6 W 21.8 W 25.4 W 28.5 W
Undervoltage lockout is confi gured by R5 connected between
the DC bus and EN/UV pin of U1. When present, switching is
inhibited until the current in the EN/UV pin exceeds 25 μA. This
allows the startup voltage to be programmed within the normal
operating input voltage range, preventing glitching of the output
under abnormal low voltage conditions and also on removal of
the AC input.
In addition to the simple input pi fi lter (C1, L1, C2) for differential
mode EMI, this design makes use of E-Shield™ shielding
techniques in the transformer to reduce common mode EMI
displacement currents, and R2 and C4 as a damping network
to reduce high frequency transformer ringing. These
techniques, combined with the frequency jitter of TNY278, give
excellent conducted and radiated EMI performance with this
design achieving >12 dBμV of margin to EN55022 Class B
conducted EMI limits.
For design fl exibility the value of C7 can be selected to pick one
of the 3 current limits options in U1. This allows the designer to
select the current limit appropriate for the application.
Standard current limit (ILIMIT) is selected with a 0.1 μF BP/M pin
capacitor and is the normal choice for typical enclosed
adapter applications.
When a 1 μF BP/M pin capacitor is used, the current limit is
reduced (ILIMITred or ILIMIT
-1) offering reduced RMS device
currents and therefore improved effi ciency, but at the expense
of maximum power capability. This is ideal for thermally
challenging designs where dissipation must be minimized.
When a 10 μF BP/M pin capacitor is used, the current limit is
increased (ILIMITinc or ILIMIT+1), extending the power capability for
applications requiring higher peak power or continuous power
where the thermal conditions allow.
Further fl exibility comes from the current limits between
adjacent TinySwitch-III family members being compatible. The
reduced current limit of a given device is equal to the standard
current limit of the next smaller device and the increased
current limit is equal to the standard current limit of the next
larger device.
Key Application Considerations
TinySwitch-lll Design Considerations
Output Power Table
The data sheet output power table (Table 1) represents the
minimum practical continuous output power level that can be
obtained under the following assumed conditions:
The minimum DC input voltage is 100 V or higher for 85 VAC
input, or 220 V or higher for 230 VAC input or 115 VAC with
a voltage doubler. The value of the input capacitance should
be sized to meet these criteria for AC input designs.
Effi ciency of 75%.
Minimum data sheet value of I2f.
Transformer primary inductance tolerance of ±10%.
Refl ected output voltage (VOR) of 135 V.
Voltage only output of 12 V with a fast PN rectifi er diode.
Continuous conduction mode operation with transient KP*
value of 0.25.
1.
2.
3.
4.
5.
6.
7.
Increased current limit is selected for peak and open frame
power columns and standard current limit for adapter
columns.
The part is board mounted with SOURCE pins soldered to a
suffi cient area of copper and/or a heatsink is used to keep
the SOURCE pin temperature at or below 110 °C.
Ambient temperature of 50 °C for open frame designs and
40 °C for sealed adapters.
*Below a value of 1, KP is the ratio of ripple to peak primary
current. To prevent reduced power capability due to premature
termination of switching cycles a transient KP limit of ≥0.25 is
recommended. This prevents the initial current limit (IINIT) from
being exceeded at MOSFET turn on.
For reference, Table 2 provides the minimum practical power
delivered from each family member at the three selectable
current limit values. This assumes open frame operation (not
thermally limited) and otherwise the same conditions as listed
above. These numbers are useful to identify the correct current
limit to select for a given device and output power requirement.
Overvoltage Protection
The output overvoltage protection provided by TinySwitch-III
uses an internal latch that is triggered by a threshold current of
approximately 5.5 mA into the BP/M pin. In addition to an
internal fi lter, the BP/M pin capacitor forms an external fi lter
providing noise immunity from inadvertent triggering. For the
bypass capacitor to be effective as a high frequency fi lter, the
capacitor should be located as close as possible to the
SOURCE and BP/M pins of the device.
For best performance of the OVP function, it is recommended
that a relatively high bias winding voltage is used, in the range
of 15 V-30 V. This minimizes the error voltage on the bias
winding due to leakage inductance and also ensures adequate
voltage during no-load operation from which to supply the
BP/M pin for reduced no-load consumption.
Selecting the Zener diode voltage to be approximately 6 V
above the bias winding voltage (28 V for 22 V bias winding)
gives good OVP performance for most designs, but can be
adjusted to compensate for variations in leakage inductance.
Adding additional fi ltering can be achieved by inserting a low
8.
9.
10.
Table 2. Minimum Practical Power at Three Selectable Current Limit Levels.
Efigflfi'fi ‘
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value (10 Ω to 47 Ω) resistor in series with the bias winding
diode and/or the OVP Zener as shown by R7 and R3 in
Figure 14. The resistor in series with the OVP Zener also limits
the maximum current into the BP/M pin.
Reducing No-load Consumption
As TinySwitch-III is self-powered from the BP/M pin capacitor,
there is no need for an auxillary or bias winding to be provided
on the transformer for this purpose. Typical no-load
consumption when self-powered is <150 mW at 265 VAC input.
The addition of a bias winding can reduce this down to <50 mW
by supplying the TinySwitch-III from the lower bias voltage and
inhibiting the internal high voltage current source. To achieve
this, select the value of the resistor (R8 in Figure 14) to provide
the data sheet DRAIN supply current. In practice, due to the
reduction of the bias voltage at low load, start with a value
equal to 40% greater than the data sheet maximum current,
and then increase the value of the resistor to give the lowest no-
load consumption.
Audible Noise
The cycle skipping mode of operation used in TinySwitch-III can
generate audio frequency components in the transformer. To
limit this audible noise generation the transformer should be
designed such that the peak core fl ux density is below
3000 Gauss (300 mT). Following this guideline and using the
standard transformer production technique of dip varnishing
practically eliminates audible noise. Vacuum impregnation of
the transformer should not be used due to the high primary
capacitance and increased losses that result. Higher fl ux
densities are possible, however careful evaluation of the audible
noise performance should be made using production
transformer samples before approving the design.
Ceramic capacitors that use dielectrics such as Z5U, when
used in clamp circuits, may also generate audio noise. If this is
the case, try replacing them with a capacitor having a different
dielectric or construction, for example a fi lm type.
TinySwitch-lll Layout Considerations
Layout
See Figure 15 for a recommended circuit board layout for
TinySwitch-III.
Single Point Grounding
Use a single point ground connection from the input fi lter
capacitor to the area of copper connected to the SOURCE pins.
Bypass Capacitor (CBP)
The BP/M pin capacitor should be located as near as possible
to the BP/M and SOURCE pins.
EN/UV Pin
Keep traces connected to the EN/UV pin short and, as far as is
practical, away from all other traces and nodes above source
potential including, but not limited to, the BYPASS and DRAIN
pins.
Primary Loop Area
The area of the primary loop that connects the input fi lter
capacitor, transformer primary and TinySwitch-III together
should be kept as small as possible.
Primary Clamp Circuit
A clamp is used to limit peak voltage on the DRAIN pin at turn
off. This can be achieved by using an RCD clamp or a Zener
(~200 V) and diode clamp across the primary winding. In all
cases, to minimize EMI, care should be taken to minimize the
circuit path from the clamp components to the transformer and
TinySwitch-III.
Thermal Considerations
The four SOURCE pins are internally connected to the IC lead
frame and provide the main path to remove heat from the
device. Therefore all the SOURCE pins should be connected to
a copper area underneath the TinySwitch-III to act not only as a
single point ground, but also as a heatsink. As this area is
connected to the quiet source node, this area should be
maximized for good heatsinking. Similarly for axial output
diodes, maximize the PCB area connected to the cathode.
Y-Capacitor
The placement of the Y-capacitor should be directly from the
primary input fi lter capacitor positive terminal to the common/
return terminal of the transformer secondary. Such a placement
will route high magnitude common mode surge currents away
from the TinySwitch-III device. Note – if an input π (C, L, C) EMI
lter is used then the inductor in the fi lter should be placed
between the negative terminals of the input fi lter capacitors.
Optocoupler
Place the optocoupler physically close to the TinySwitch-III to
minimizing the primary-side trace lengths. Keep the high
current, high voltage drain and clamp traces away from the
optocoupler to prevent noise pick up.
Output Diode
For best performance, the area of the loop connecting the
secondary winding, the output diode and the output fi lter
capacitor, should be minimized. In addition, suf cient copper
area should be provided at the anode and cathode terminals of
the diode for heatsinking. A larger area is preferred at the quiet
cathode terminal. A large anode area can increase high
frequency radiated EMI.
PC Board Leakage Currents
TinySwitch-III is designed to optimize energy ef ciency across
the power range and particularly in standby/no-load conditions.
Current consumption has therefore been minimized to achieve
this performance. The EN/UV pin undervoltage feature for
example has a low threshold (~1 μA) to detect whether an
undervoltage resistor is present.
Parasitic leakage currents into the EN/UV pin are normally well
below this 1 μA threshold when PC board assembly is in a well
controlled production facility. However, high humidity
conditions together with board and/or package contamination,
either from no-clean fl ux or other contaminants, can reduce the
surface resistivity enough to allow parasitic currents >1 μA to
ow into the EN/UV pin. These currents can fl ow from higher
voltage exposed solder pads close to the EN/UV pin such as
Inpul FHIev Capacxlov V V | newsg- 1mm": w m
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the BP/M pin solder pad preventing the design from starting up.
Designs that make use of the undervoltage lockout feature by
connecting a resistor from the high voltage rail to the EN/UV pin
are not affected.
If the contamination levels in the PC board assembly facility are
unknown, the application is open frame or operates in a high
pollution degree environment and the design does not make
use of the undervoltage lockout feature, then an optional
390 kΩ resistor should be added from EN/UV pin to SOURCE
pin to ensure that the parasitic leakage current into the EN/UV
pin is well below 1 μA.
Note that typical values for surface insulation resistance (SIR)
where no-clean fl ux has been applied according to the
suppliers’ guidelines are >>10 MΩ and do not cause this issue.
Quick Design Checklist
As with any power supply design, all TinySwitch-III designs
should be verifi ed on the bench to make sure that component
specifi cations are not exceeded under worst case conditions.
The following minimum set of tests is strongly recommended:
Maximum drain voltage – Verify that VDS does not exceed
650 V at highest input voltage and peak (overload) output
power. The 50 V margin to the 700 V BVDSS specifi cation
gives margin for design variation.
1.
Figure 15. Recommended Circuit Board Layout for TinySwitch-III with Undervoltage Lock Out Resistor.
TOP VIEW
PI-4368-042506
Opto-
coupler
+
-
HV
+- DC
OUT
Input Filter Capacitor
Output
Rectifier
Safety Spacing
T
r
a
n
s
f
o
r
m
e
r
PRI
SEC
BIAS
D
Output Filter
Capacitor
Maximize hatched copper
areas ( ) for optimum
heatsinking
BP/M
EN/UV
Y1-
Capacitor
S
S
S
S
PRI
CBP
BIAS
TinySwitch-III
Maximum drain current – At maximum ambient temperature,
maximum input voltage and peak output (overload) power,
verify drain current waveforms for any signs of transformer
saturation and excessive leading edge current spikes at
startup. Repeat under steady state conditions and verify that
the leading edge current spike event is below ILIMIT(Min) at the
end of the tLEB(Min). Under all conditions, the maximum drain
current should be below the specifi ed absolute maximum
ratings.
Thermal Check – At specifi ed maximum output power,
minimum input voltage and maximum ambient temperature,
verify that the temperature specifi cations are not exceeded
for TinySwitch-III, transformer, output diode, and output
capacitors. Enough thermal margin should be allowed for
part-to-part variation of the RDS(ON) of TinySwitch-III as
specifi ed in the data sheet. Under low line, maximum power,
a maximum TinySwitch-III SOURCE pin temperature of
110 °C is recommended to allow for these variations.
Design Tools
Up-to-date information on design tools is available at the Power
Integrations website: www.powerint.com.
2.
3.
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Absolute Maximum Ratings(1,4)
DRAIN Voltage .............................................................................. -0.3 V to 700 V
DRAIN Peak Current: TNY274 ....................................... 400 (750) mA(2)
TNY275 .....................................560 (1050) mA(2)
TNY276 ..................................... 720 (1350) mA(2)
TNY277 .....................................880 (1650) mA(2)
TNY278 .................................. 1040 (1950) mA(2)
TNY279 ................................. 1200 (2250) mA(2)
TNY280 ................................ 1360 (2550) mA(2)
EN/UV Voltage ................................................................................... -0.3 V to 9 V
EN/UV Current ........................................................... .................................. 100 mA
BP/M Voltage .................................................. ....................................-0.3 V to 9 V
Storage Temperature .............................................................-65 °C to 150 °C
Operating Junction Temperature(3) ............................... -40 °C to 150 °C
Lead Temperature(4) .....................................................................................260 °C
Notes:
1. All voltages referenced to SOURCE, TA = 25 °C.
2. The higher peak DRAIN current is allowed while the DRAIN
voltage is simultaneously less than 400 V.
3. Normally limited by internal circuitry.
4. 1/16 in. from case for 5 seconds.
5. Maximum ratings specifi ed may be applied one at a time,
without causing permanent damage to the product. Exposure
to Absolute Rating conditions for extended periods of time may
affect product reliability.
Thermal Impedance
Thermal Impedance: P or G Package:
(θJA) ............................ ....................70 °C/W(2); 60 °C/W(3)
(θJC)(1) ............................................... ............................11 °C/W
Notes:
1. Measured on the SOURCE pin close to plastic interface.
2. Soldered to 0.36 sq. in. (232 mm2), 2 oz. (610 g/m2) copper clad.
3. Soldered to 1 sq. in. (645 mm2), 2 oz. (610 g/m2) copper clad.
Parameter Symbol
Conditions
SOURCE = 0 V; TJ = -40 to 125 °C
See Figure 16
(Unless Otherwise Specifi ed)
Min Typ Max Units
Control Functions
Output Frequency
in Standard Mode fOSC
TJ = 25 °C
See Figure 4
Average 124 132 140
kHz
Peak-to-peak Jitter 8
Maximum Duty Cycle DCMAX S1 Open 62 65 %
EN/UV Pin Upper
Turnoff Threshold
Current
IDIS -150 -115 -90 μA
EN/UV Pin
Voltage VEN
IEN/UV = 25 μA1.8 2.2 2.6
V
IEN/UV = -25 μA0.8 1.2 1.6
DRAIN Supply Current
IS1
EN/UV Current > IDIS (MOSFET Not
Switching) See Note A 290 μA
IS2
EN/UV Open
(MOSFET
Switching at fOSC)
See Note B
TNY274 275 360
μA
TNY275 295 400
TNY276 310 430
TNY277 365 460
TNY278 445 540
TNY279 510 640
TNY280 630 760
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Parameter Symbol
Conditions
SOURCE = 0 V; TJ = -40 to 125 °C
See Figure 16
(Unless Otherwise Specifi ed)
Min Typ Max Units
Control Functions (cont.)
BP/M Pin Charge
Current
ICH1
VBP/M = 0 V,
TJ = 25 °C
See Note C, D
TNY274 -6 -3.8 -1.8
mA
TNY275-278 -8.3 -5.4 -2.5
TNY279-280 -9.7 -6.8 -3.9
ICH2
VBP/M = 4 V,
TJ = 25 °C
See Note C, D
TNY274 -4.1 -2.3 -1
TNY275-278 -5 -3.5 -1.5
TNY279-280 -6.6 -4.6 -2.1
BP/M Pin Voltage VBP/M See Note C 5.6 5.85 6.15 V
BP/M Pin Voltage
Hysteresis VBP/MH 0.80 0.95 1.20 V
BP/M Pin Shunt
Voltage VSHUNT IBP = 2 mA 6.0 6.4 6.7 V
EN/UV Pin Line Under-
voltage Threshold ILUV TJ = 25 °C 22.5 25 27.5 μA
Circuit Protection
Standard Current Limit
(BP/M Capacitor =
0.1 μF) See Note D
ILIMIT
di/dt = 50 mA/μs
TJ = 25 °C
See Note E
TNY274P 233 250 267
mA
TNY274G 233 250 273
di/dt = 55 mA/μs
TJ = 25 °C
See Note E
TNY275P 256 275 294
TNY275G 256 275 300
di/dt = 70 mA/μs
TJ = 25 °C
See Note E
TNY276P 326 350 374
TNY276G 326 350 382
di/dt = 90 mA/μs
TJ = 25 °C
See Note E
TNY277P 419 450 481
TNY277G 419 450 491
di/dt = 110 mA/μs
TJ = 25 °C
See Note E
TNY278P 512 550 588
TNY278G 512 550 600
di/dt = 130 mA/μs
TJ = 25 °C
See Note E
TNY279P 605 650 695
TNY279G 605 650 709
di/dt = 150 mA/μs
TJ = 25 °C
See Note E
TNY280P 698 750 802
TNY280G 698 750 818
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TNY274-280
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Parameter Symbol
Conditions
SOURCE = 0 V; TJ = -40 to 125 °C
See Figure 16
(Unless Otherwise Specifi ed)
Min Typ Max Units
Circuit Protection (cont.)
Reduced Current Limit
(BP/M Capacitor =
1 μF) See Note D
ILIMITred
di/dt = 50 mA/μs
TJ = 25 °C
See Note E
TNY274P 196 210 233
mA
TNY274G 196 210 237
di/dt = 55 mA/μs
TJ = 25 °C
See Note E
TNY275P 233 250 277
TNY275G 233 250 283
di/dt = 70 mA/μs
TJ = 25 °C
See Notes E
TNY276P 256 275 305
TNY276G 256 275 311
di/dt = 90 mA/μs
TJ = 25 °C
See Notes E
TNY277P 326 350 388
TNY277G 326 350 396
di/dt = 110 mA/μs
TJ = 25 °C
See Notes E
TNY278P 419 450 499
TNY278G 419 450 509
di/dt = 130 mA/μs
TJ = 25 °C
See Notes E
TNY279P 512 550 610
TNY279G 512 550 622
di/dt = 150 mA/μs
TJ = 25 °C
See Notes E
TNY280P 605 650 721
TNY280G 605 650 735
Increased Current Limit
(BP/M Capacitor =
10 μF) See Note D
ILIMITinc
di/dt = 50 mA/μs
TJ = 25 °C
See Notes E, F
TNY274P 196 210 233
mA
TNY274G 196 210 237
di/dt = 55 mA/μs
TJ = 25 °C
See Notes E
TNY275P 326 350 388
TNY275G 326 350 396
di/dt = 70 mA/μs
TJ = 25 °C
See Notes E
TNY276P 419 450 499
TNY276G 419 450 509
di/dt = 90 mA/μs
TJ = 25 °C
See Notes E
TNY277P 512 550 610
TNY277G 512 550 622
di/dt = 110 mA/μs
TJ = 25 °C
See Notes E
TNY278P 605 650 721
TNY278G 605 650 735
di/dt = 130 mA/μs
TJ = 25 °C
See Notes E
TNY279P 698 750 833
TNY279G 698 750 848
di/dt = 150 mA/μs
TJ = 25 °C
See Notes E
TNY280P 791 850 943
TNY280G 791 850 961
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Parameter Symbol
Conditions
SOURCE = 0 V; TJ = -40 to 125 °C
See Figure 16
(Unless Otherwise Specifi ed)
Min Typ Max Units
Circuit Protection (cont.)
Power Coeffi cient I2f
Standard Current
Limit, I2f = ILIMIT(TYP)
2
× fOSC(TYP)
TJ = 25 °C
TNY274-280P 0.9 ×
I2fI2f1.12 ×
I2f
A2Hz
TNY274-280G 0.9 ×
I2fI2f1.16 ×
I2f
Reduced Current
Limit, I2f = ILIMITred(TYP)
2
× fOSC(TYP)
TJ = 25 °C
TNY274-280P 0.9 ×
I2fI2f1.16 ×
I2f
TNY274-280G 0.9 ×
I2fI2f1.20 ×
I2f
Increased Current
Limit, I2f = ILIMITinc(TYP)
2
× fOSC(TYP)
TJ = 25 °C
TNY274-280P 0.9 ×
I2fI2f1.16 ×
I2f
TNY274-280G 0.9 ×
I2fI2f1.20 ×
I2f
Initial Current Limit IINIT
See Figure 19
TJ = 25 °C, See Note G
0.75 ×
ILIMIT(MIN)
mA
Leading Edge
Blanking Time tLEB
TJ = 25 °C
See Note G 170 215 ns
Current Limit
Delay tILD
TJ = 25 °C
See Note G, H 150 ns
Thermal Shutdown
Temperature TSD 135 142 150 °C
Thermal Shutdown
Hysteresis TSDH 75 °C
BP/M Pin Shutdown
Threshold Current ISD 4 6.5 9 mA
BP/M Pin Power up
Reset Threshold
Voltage
VBP/M(RESET) 1.6 2.6 3.6 V
Output
ON-State
Resistance RDS(ON)
TNY274
ID = 25 mA
TJ = 25 °C 28 32
Ω
TJ = 100 °C 42 48
TNY275
ID = 28 mA
TJ = 25 °C 19 22
TJ = 100 °C 29 33
TNY276
ID = 35 mA
TJ = 25 °C 14 16
TJ = 100 °C 21 24
Efigflfi'fi ‘
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TNY274-280
www.powerint.com
Parameter Symbol
Conditions
SOURCE = 0 V; TJ = -40 to 125 °C
See Figure 16
(Unless Otherwise Specifi ed)
Min Typ Max Units
Output (cont.)
ON-State
Resistance RDS(ON)
TNY277
ID = 45 mA
TJ = 25 °C 7.8 9.0
Ω
TJ = 100 °C 11.7 13.5
TNY278
ID = 55 mA
TJ = 25 °C 5.2 6.0
TJ = 100 °C 7.8 9.0
TNY279
ID = 65 mA
TJ = 25 °C 3.9 4.5
TJ = 100 °C 5.8 6.7
TNY280
ID = 75 mA
TJ = 25 °C 2.6 3.0
TJ = 100 °C 3.9 4.5
OFF-State Drain
Leakage Current
IDSS1
VBP/M = 6.2 V
VEN/UV = 0 V
VDS = 560 V
TJ = 125 °C
See Note I
TNY274-276 50
μA
TNY277-278 100
TNY279-280 200
IDSS2
VBP/M = 6.2 V
VEN/UV = 0 V
VDS = 375 V,
TJ = 50 °C
See Note G, I
15
Breakdown
Voltage BVDSS
VBP = 6.2 V, VEN/UV = 0 V,
See Note J, TJ = 25 °C 700 V
DRAIN Supply
Voltage 50 V
Auto-Restart
ON-Time at fOSC
tAR
TJ = 25 °C
See Note K 64 ms
Auto-Restart
Duty Cycle DCAR TJ = 25 °C 3 %
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NOTES:
IS1 is an accurate estimate of device controller current consumption at no-load, since operating frequency is so low under these
conditions. Total device consumption at no-load is the sum of IS1 and IDSS2.
Since the output MOSFET is switching, it is diffi cult to isolate the switching current from the supply current at the DRAIN. An
alternative is to measure the BP/M pin current at 6.1 V.
BP/M pin is not intended for sourcing supply current to external circuitry.
To ensure correct current limit it is recommended that nominal 0.1 μF / 1 μF / 10 μF capacitors are used. In addition, the BP/M
capacitor value tolerance should be equal or better than indicated below across the ambient temperature range of the target
application. The minimum and maximum capacitor values are guaranteed by characterization.
For current limit at other di/dt values, refer to Figure 23.
TNY274 does not set an increased current limit value, but with a 10 μF BP/M pin capacitor the current limit is the same as with a
1 μF BP/M pin capacitor (reduced current limit value).
This parameter is derived from characterization.
This parameter is derived from the change in current limit measured at 1X and 4X of the di/dt shown in the ILIMIT specifi cation.
IDSS1 is the worst case OFF state leakage specifi cation at 80% of BVDSS and maximum operating junction temperature. IDSS2 is a
typical specifi cation under worst case application conditions (rectifi ed 265 VAC) for no-load consumption calculations.
Breakdown voltage may be checked against minimum BVDSS specifi cation by ramping the DRAIN pin voltage up to but not
exceeding minimum BVDSS.
Auto-restart on time has the same temperature characteristics as the oscillator (inversely proportional to frequency).
A.
B.
C.
D.
E.
F.
G.
H.
I.
J.
K.
Nominal BP/M
Pin Cap Value
Tolerance Relative to Nominal
Capacitor Value
Min Max
0.1 μF-60% +100%
1 μF-50% +100%
10 μF-50% NA
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TNY274-280
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PI-4079-080905
0.1 μF
10 V
50 V
470 Ω
5 W S2
470 Ω
NOTE: This test circuit is not applicable for current limit or output characteristic measurements.
SD
EN/UV
S
SBP/M
S
150 V
S1
2 MΩ
PI-2364-012699
EN/UV
tP
tEN/UV
DCMAX
tP = 1
fOSC
VDRAIN
(internal signal)
Figure 16. General Test Circuit.
Figure 17. Duty Cycle Measurement. Figure 18. Output Enable Timing.
0.8
PI-4279-013006
Figure 19. Current Limit Envelope.
TNV275 TNv27s 7 TNV277 TNV27B TNV279 7 TNVQEO 1,5 2,0 3,5 5,5 7,3 11 Eflgfllfifl '
Rev. I 01/09
19
TNY274-280
www.powerint.com
1.1
1.0
0.9
-50 -25 0 25 50 75 100 125 150
Junction Temperature (°C)
Breakdown Voltage
(Normalized to 25 °C)
PI-2213-012301
1
0.8
0.6
0.4
0.2
0
-50 0 50 100 150
Temperature (°C)
PI-4102-010906
1.2
Standard Current Limit
(Normalized to 25 °C)
Figure 20. Breakdown vs. Temperature.
Figure 22. Standard Current Limit vs. Temperature.
Figure 21. Frequency vs. Temperature.
1.2
1.0
0.8
0.6
0.4
0.2
0
-50 -25 0 25 50 75 100 125
Junction Temperature (°C)
PI-4280-012306
Output Frequency
(Normalized to 25 °C)
Figure 23. Current Limit vs. di/dt.
1.4
1.2
1.0
0.8
0.6
0.4
0.2
0
1234
Normalized di/dt
PI-4081-082305
Normalized Current Limit
TNY274 50 mA/μs
TNY275 55 mA/μs
TNY276 70 mA/μs
TNY277 90 mA/μs
TNY278 110 mA/μs
TNY279 130 mA/μs
TNY280 150 mA/μs
Normalized
di/dt = 1
Note: For the
normalized current
limit value, use the
typical current limit
specified for the
appropriate BP/M
capacitor.
DRAIN Voltage (V)
Drain Current (mA)
300
250
200
100
50
150
0
0246810
T
CASE
=25 °C
T
CASE
=100 °C
PI-4082-082305
TNY274 1.0
TNY275 1.5
TNY276 2.0
TNY277 3.5
TNY278 5.5
TNY279 7.3
TNY280 11
Scaling Factors:
Figure 24. Output Characteristic.
Figure 25. COSS vs. Drain Voltage.
Drain Voltage (V)
Drain Capacitance (pF)
PI-4083-082305
0 100 200 300 400 500 600
1
10
100
1000
TNY274 1.0
TNY275 1.5
TNY276 2.0
TNY277 3.5
TNY278 5.5
TNY279 7.3
TNY280 11
Scaling Factors:
7 (1.22) \ Ii:— EWWFF A
Rev. I 01/09
20
TNY274-280
www.powerint.com
Notes:
1. Package dimensions conform to JEDEC specification
MS-001-AB (Issue B 7/85) for standard dual-in-line (DIP)
package with .300 inch row spacing.
2. Controlling dimensions are inches. Millimeter sizes are
shown in parentheses.
3. Dimensions shown do not include mold flash or other
protrusions. Mold flash or protrusions shall not exceed
.006 (.15) on any side.
4. Pin locations start with Pin 1, and continue counter-clock-
wise to Pin 8 when viewed from the top. The notch and/or
dimple are aids in locating Pin 1. Pin 3 is omitted.
5. Minimum metal to metal spacing at the package body for
the omitted lead location is .137 inch (3.48 mm).
6. Lead width measured at package body.
7. Lead spacing measured with the leads constrained to be
perpendicular to plane T.
.008 (.20)
.015 (.38)
.300 (7.62) BSC
(NOTE 7)
.300 (7.62)
.390 (9.91)
.367 (9.32)
.387 (9.83)
.240 (6.10)
.260 (6.60)
.125 (3.18)
.145 (3.68)
.057 (1.45)
.068 (1.73)
.120 (3.05)
.140 (3.56)
.015 (.38)
MINIMUM
.048 (1.22)
.053 (1.35)
.100 (2.54) BSC
.014 (.36)
.022 (.56)
-E-
Pin 1
SEATING
PLANE
-D-
-T-
P08C
DIP-8C
PI-3933-100504
D S .004 (.10)
T E D S .010 (.25) M
(NOTE 6)
.137 (3.48)
MINIMUM
50
30
40
10
20
0
0 200 400 600
DRAIN Voltage (V)
Power (mW)
PI-4084-082305
TNY274 1.0
TNY275 1.5
TNY276 2.0
TNY277 3.5
TNY278 5.5
TNY279 7.3
TNY280 11
Scaling Factors:
1.2
1.0
0.8
0.6
0.4
0.2
0
-50 -25 0 25 50 75 100 125
Junction Temperature (°C)
PI-4281-012306
Under-Voltage Threshold
(Normalized to 25 °C)
Figure 27. Undervoltage Threshold vs. Temperature.
Figure 26. Drain Capacitance Power.
Rev. I 01/09
21
TNY274-280
www.powerint.com
SMD-8C
PI-4015-013106
.004 (.10)
.012 (.30)
.036 (0.91)
.044 (1.12)
.004 (.10)
0 -
° 8
°
.367 (9.32)
.387 (9.83)
.048 (1.22) .009 (.23)
.053 (1.35)
.032 (.81)
.037 (.94)
.125 (3.18)
.145 (3.68)
-D-
Notes:
1. Controlling dimensions are
inches. Millimeter sizes are
shown in parentheses.
2. Dimensions shown do not
include mold flash or other
protrusions. Mold flash or
protrusions shall not exceed
.006 (.15) on any side.
3. Pin locations start with Pin 1,
and continue counter-clock-
wise to Pin 8 when viewed
from the top. Pin 3 is omitted.
4. Minimum metal to metal
spacing at the package body
for the omitted lead location
is .137 inch (3.48 mm).
5. Lead width measured at
package body.
6. D and E are referenced
datums on the package
body.
.057 (1.45)
.068 (1.73)
(NOTE 5)
E S
.100 (2.54) (BSC)
.372 (9.45)
.240 (6.10) .388 (9.86)
.260 (6.60) .010 (.25)
-E-
Pin 1
D S .004 (.10)
G08C
.420
.046 .060 .060 .046
.080
Pin 1
.086
.186
.286
Solder Pad Dimensions
.137 (3.48)
MINIMUM
Part Ordering Information
• TinySwitch Product Family
• Series Number
• Package Identifi er
G Plastic Surface Mount SMD-8C
P Plastic DIP-8C
Lead Finish
N Pure Matte Tin (Pb-Free)
G RoHS compliant and Halogen Free (P package only)
• Tape & Reel and Other Options
Blank Standard Confi guration
TL Tape & Reel, 1000 pcs min./mult., G package only
TNY 278 G N - TL
Efigflfi'fi ‘
Rev. I 01/09
22
TNY274-280
www.powerint.com
Eflgfllfifi ‘
Rev. I 01/09
23
TNY274-280
www.powerint.com
Revision Notes Date
D Release fi nal data sheet. 1/06
E Corrected fi gure numbers and references. 2/06
FSeparated current limit and power coef cient values for G package and updated Figure 15. Added
EN/UV and PC board leakage currents in Key Applications Considerations section. 4/06
G Updated line undervoltage current threshold to 2 mA. 6/06
H Updated BP/M Pin Charge current and Power Coeffi cient sections of Parameter Tables. 9/08
I Updated Part Ordering Information section with Halogen Free. 1/09
For the latest updates, visit our website: www.powerint.com
Power Integrations reserves the right to make changes to its products at any time to improve reliability or manufacturability. Power
Integrations does not assume any liability arising from the use of any device or circuit described herein. POWER INTEGRATIONS MAKES
NO WARRANTY HEREIN AND SPECIFICALLY DISCLAIMS ALL WARRANTIES INCLUDING, WITHOUT LIMITATION, THE IMPLIED
WARRANTIES OF MERCHANTABILITY, FITNESS FOR A PARTICULAR PURPOSE, AND NON-INFRINGEMENT OF THIRD PARTY RIGHTS.
Patent Information
The products and applications illustrated herein (including transformer construction and circuits external to the products) may be covered
by one or more U.S. and foreign patents, or potentially by pending U.S. and foreign patent applications assigned to Power Integrations. A
complete list of Power Integrations patents may be found at www.powerint.com. Power Integrations grants its customers a license under
certain patent rights as set forth at http://www.powerint.com/ip.htm.
Life Support Policy
POWER INTEGRATIONS PRODUCTS ARE NOT AUTHORIZED FOR USE AS CRITICAL COMPONENTS IN LIFE SUPPORT DEVICES OR
SYSTEMS WITHOUT THE EXPRESS WRITTEN APPROVAL OF THE PRESIDENT OF POWER INTEGRATIONS. As used herein:
A Life support device or system is one which, (i) is intended for surgical implant into the body, or (ii) supports or sustains life, and (iii)
whose failure to perform, when properly used in accordance with instructions for use, can be reasonably expected to result in signifi cant
injury or death to the user.
A critical component is any component of a life support device or system whose failure to perform can be reasonably expected to cause
the failure of the life support device or system, or to affect its safety or effectiveness.
The PI logo, TOPSwitch, TinySwitch, LinkSwitch, DPA-Switch, PeakSwitch, EcoSmart, Clampless, E-Shield, Filterfuse, StakFET, PI Expert
and PI FACTS are trademarks of Power Integrations, Inc. Other trademarks are property of their respective companies.
©2006, Power Integrations, Inc.
1.
2.
Power Integrations Worldwide Sales Support Locations
World Headquarters
5245 Hellyer Avenue
San Jose, CA 95138, USA.
Main: +1-408-414-9200
Customer Service:
Phone: +1-408-414-9665
Fax: +1-408-414-9765
e-mail: usasales@powerint.com
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