LMH6552 Datasheet by Texas Instruments

V'.‘ ‘F. B I TEXAS INSTRUMENTS 274 1279
127:
+
-
LMH6552
V+
V-
22 pF
VREF
127:
-
+
100:
100:
274:
274:
ADC14DS105
14-Bit
105
MSPS
620 nH
620 nH
49.9:
68.1:
68.1:
0.1 PF
50:
Single-Ended
AC-coupled
Source
Copyright © 2016, Texas Instruments Incorporated
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An IMPORTANT NOTICE at the end of this data sheet addresses availability, warranty, changes, use in safety-critical applications,
intellectual property matters and other important disclaimers. PRODUCTION DATA.
LMH6552
SNOSAX9J APRIL 2007REVISED APRIL 2016
LMH6552 1.5-GHz Fully Differential Amplifier
1
1 Features
1 1.5-GHz 3 dB Small Signal
Bandwidth at AV= 1
1.25-GHz 3 dB Large Signal
Bandwidth at AV= 1
800-MHz Bandwidth at AV= 4
450-MHz 0.1 dB Flatness
3800-V/µs Slew Rate
10-ns Settling Time to 0.1%
90 dB THD at 20 MHz
74 dB THD at 70 MHz
20-ns Enable/Shutdown Pin
5-V to 12-V Operation
2 Applications
Differential ADC Driver
Video Over Twisted Pair
Differential Line Driver
Single End to Differential Converter
High-Speed Differential Signaling
IF/RF Amplifier
Level Shift Amplifier
SAW Filter Buffer/Driver
3 Description
The LMH6552 device is a high-performance, fully
differential amplifier designed to provide the
exceptional signal fidelity and wide large-signal
bandwidth necessary for driving 8-bit to 14-bit high-
speed data acquisition systems. Using TI's
proprietary differential current mode input stage
architecture, the LMH6552 allows operation at gains
greater than unity without sacrificing response
flatness, bandwidth, harmonic distortion, or output
noise performance.
With external gain set resistors and integrated
common mode feedback, the LMH6552 can be
configured as either a differential input to differential
output or single-ended input to differential output gain
block. The LMH6552 can be AC- or DC-coupled at
the input which makes it suitable for a wide range of
applications, including communication systems and
high-speed oscilloscope front ends. The performance
of the LMH6552 driving an ADC14DS105 device is
86 dBc SFDR and 74 dBc SNR up to 40 MHz.
The LMH6552 is available in an 8-pin SOIC package
as well as a space-saving, thermally enhanced 8-pin
WSON package for higher performance.
Device Information(1)
PART NUMBER PACKAGE BODY SIZE (NOM)
LMH6552 SOIC (8) 4.90 mm × 3.91 mm
WSON (8) 3.00 mm × 2.50 mm
(1) For all available packages, see the orderable addendum at
the end of the datasheet.
Typical Application Schematic
l TEXAS INSTRUMENTS
2
LMH6552
SNOSAX9J APRIL 2007REVISED APRIL 2016
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Table of Contents
1 Features.................................................................. 1
2 Applications ........................................................... 1
3 Description ............................................................. 1
4 Revision History..................................................... 2
5 Pin Configuration and Functions......................... 3
6 Specifications......................................................... 4
6.1 Absolute Maximum Ratings ...................................... 4
6.2 ESD Ratings.............................................................. 4
6.3 Recommended Operating Conditions....................... 4
6.4 Thermal Information.................................................. 4
6.5 Electrical Characteristics: ±5 V ................................. 5
6.6 Electrical Characteristics: ±2.5 V .............................. 7
6.7 Typical Characteristics V+= +5 V, V=5 V ........... 9
7 Detailed Description............................................ 16
7.1 Overview ................................................................. 16
7.2 Functional Block Diagram....................................... 16
7.3 Feature Description................................................. 16
7.4 Device Functional Modes........................................ 17
8 Application and Implementation ........................ 17
8.1 Application Information............................................ 17
8.2 Typical Applications ................................................ 17
9 Power Supply Recommendations...................... 26
9.1 Power Supply Bypassing ........................................ 26
10 Layout................................................................... 27
10.1 Layout Guidelines ................................................. 27
10.2 Layout Example .................................................... 28
10.3 Thermal Considerations........................................ 29
10.4 Power Dissipation ................................................. 29
10.5 ESD Protection...................................................... 30
11 Device and Documentation Support ................. 31
11.1 Device Support...................................................... 31
11.2 Documentation Support ........................................ 31
11.3 Community Resources.......................................... 31
11.4 Trademarks........................................................... 31
11.5 Electrostatic Discharge Caution............................ 31
11.6 Glossary................................................................ 31
12 Mechanical, Packaging, and Orderable
Information ........................................................... 31
4 Revision History
NOTE: Page numbers for previous revisions may differ from page numbers in the current version.
Changes from Revision I (January 2015) to Revision J Page
Changed footnote 4 in Electrical Characteristics: ±5 V table ................................................................................................. 5
Changed Miscellaneous Performance, Enable Voltage Threshold parameter minimum specification in Electrical
Characteristics: ±5 V table...................................................................................................................................................... 6
Changed footnote 4 in Electrical Characteristics: ±2.5 V table ............................................................................................. 7
Changed minimum specifications of Miscellaneous Performance, Enable Voltage Threshold and Disable Voltage
Threshold parameters in Electrical Characteristics: ±2.5 V table .......................................................................................... 8
Added Community Resources section ................................................................................................................................ 31
Changes from Revision H (March 2013) to Revision I Page
Added ESD Ratings table, Feature Description section, Device Functional Modes,Application and Implementation
section, Power Supply Recommendations section, Layout section, Device and Documentation Support section, and
Mechanical, Packaging, and Orderable Information section.................................................................................................. 1
Changes from Revision G (March 2013) to Revision H Page
Changed layout of National Data Sheet to TI format ........................................................................................................... 27
l TEXAS INSTRUMENTS flI—lflfl
1
4
3
5
8
7
6
V+
+ OUT
VCM
- IN
- OUT
+ IN
EN
V-
2
DAP
-
4
+OUT 5-OUT
36
V+ V-
EN
27
VCM
+
18
-IN +IN
3
LMH6552
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5 Pin Configuration and Functions
D Package
8 Pins
Top View
NGS Package
8 Pins
Top View
Pin Functions
PIN DESCRIPTION
NAME NO.
EN 7 Enable
-IN 1 Negative Input
+IN 8 Positive Input
-OUT 5 Negative Output
+OUT 4 Positive Output
V- 6 Negative Supply
V+ 3 Positive Supply
VCM 2 Output Common Mode Control
DAP DAP Die Attach Pad (See Thermal Considerations for more information)
l TEXAS INSTRUMENTS
4
LMH6552
SNOSAX9J APRIL 2007REVISED APRIL 2016
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(1) Stresses beyond those listed under Absolute Maximum Ratings may cause permanent damage to the device. These are stress ratings
only, which do not imply functional operation of the device at these or any other conditions beyond those indicated under Recommended
Operating Conditions. Exposure to absolute-maximum-rated conditions for extended periods may affect device reliability.
(2) For soldering specifications see SNOA549
(3) The maximum output current (IOUT) is determined by device power dissipation limitations. See Power Dissipation for more details.
6 Specifications
6.1 Absolute Maximum Ratings(1)(2)
MIN MAX UNIT
Supply Voltage 13.2 V
Common Mode Input Voltage ±VSV
Maximum Input Current (pins 1, 2, 7, 8) 30 mA
Maximum Output Current (pins 4, 5) (3) mA
Maximum Junction Temperature 150 °C
Storage temperature, Tstg 65 150 °C
(1) JEDEC document JEP155 states that 500-V HBM allows safe manufacturing with a standard ESD control process.
(2) JEDEC document JEP157 states that 250-V CDM allows safe manufacturing with a standard ESD control process.
6.2 ESD Ratings
VALUE UNIT
V(ESD) Electrostatic discharge
Human-body model (HBM), per ANSI/ESDA/JEDEC JS-001(1) ±2000
V
Charged-device model (CDM), per JEDEC specification JESD22-
C101(2) ±750
Machine model (MM) ±250
(1) The maximum power dissipation is a function of TJ(MAX),θJA. The maximum allowable power dissipation at any ambient temperature is
PD= (TJ(MAX)– TA) / θJA. All numbers apply for packages soldered directly onto a PC Board.
6.3 Recommended Operating Conditions
MIN NOM MAX UNIT
Operating Temperature Range (1) 40 +85 °C
Total Supply Voltage 4.5 12 V
(1) For more information about traditional and new thermal metrics, see the IC Package Thermal Metrics application report, SPRA953.
6.4 Thermal Information
THERMAL METRIC(1)
LMH6552
UNITD NGS
8 PINS 8 PINS
RθJA Junction-to-ambient thermal resistance 150 58 °C/W
l TEXAS INSTRUMENTS
5
LMH6552
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(1) Electrical Table values apply only for factory testing conditions at the temperature indicated. Factory testing conditions result in very
limited self-heating of the device such that TJ= TA. No specification of parametric performance is indicated in the electrical tables under
conditions of internal self-heating where TJ> TA. See Overview for information on temperature de-rating of this device. Min/Max ratings
are based on product characterization and simulation. Individual parameters are tested as noted.
(2) Limits are 100% production tested at 25°C. Limits over the operating temperature range are ensured through correlation using Statistical
Quality Control (SQC) methods.
(3) Typical values represent the most likely parametric norm as determined at the time of characterization. Actual typical values can vary
over time and also depend on the application and configuration. The typical values are not tested and are not ensured on shipped
production material.
(4) IBoffset is referred to a differential output offset voltage by the following relationship: VOD(offset) = IBI*2RF.
6.5 Electrical Characteristics: ±5 V
Unless otherwise specified, all limits are ensured for TA= 25°C, V+= +5 V, V=5 V, AV= 1, VCM = 0 V, RF= RG= 357 , RL
= 500 , for single ended in, differential out.(1)
PARAMETER TEST CONDITIONS MIN(2) TYP(3) MAX(2) UNIT
AC PERFORMANCE (DIFFERENTIAL)
SSBW Small Signal 3-dB Bandwidth (2) VOUT = 0.2 VPP, AV= 1, RL= 1 k1500
MHz
VOUT = 0.2 VPP, AV= 1 1000
VOUT = 0.2 VPP, AV= 2 930
VOUT = 0.2 VPP, AV= 4 810
VOUT = 0.2 VPP, AV= 8 590
LSBW Large Signal 3 dB Bandwidth VOUT = 2 VPP, AV= 1, RL= 1 k1250
MHz
VOUT = 2 VPP, AV= 1 950
VOUT = 2 VPP, AV= 2 820
VOUT = 2 VPP, AV= 4 740
VOUT = 2 VPP, AV= 8 590
0.1-dB Bandwidth VOUT = 0.2 VPP, AV= 1 450 MHz
Slew Rate 4-V Step, AV= 1 3800 V/μs
Rise, Fall Time, 10%-90% 2-V Step 600 ps
0.1% Settling Time 2-V Step 10 ns
Overdrive Recovery Time VIN = 1.8-V to 0-V Step, AV= 5 V/V 6 ns
DISTORTION AND NOISE RESPONSE
HD2 2nd Harmonic Distortion VOUT = 2 VPP, f = 20 MHz, RL= 800 –92 dBc
VOUT = 2 VPP, f = 70 MHz, RL= 800 –74
HD3 3rd Harmonic Distortion VOUT = 2 VPP, f = 20 MHz, RL= 800 –93 dBc
VOUT = 2 VPP, f = 70 MHz, RL= 800 –84
IMD3 Two-Tone Intermodulation f 70 MHz, Third-Order Products, VOUT =
2-VPP Composite –87 dBc
Input Noise Voltage f 1 MHz 1.1 nV/Hz
Input Noise Current f 1 MHz 19.5 pA/Hz
Noise Figure (See Figure 46) 50-System, AV= 9, 10 MHz 10.3 dB
INPUT CHARACTERISTICS
IBI Input Bias Current (4) 60 110 µA
IBoffset Input Bias Current Differential
(3) VCM = 0 V, VID = 0 V, IBoffset = (IB- IB+)/2 2.5 18 µA
CMRR Common Mode Rejection Ratio (3) DC, VCM = 0 V, VID = 0 V 80 dBc
RIN Input Resistance Differential 15
CIN Input Capacitance Differential 0.5 pF
CMVR Input Common Mode Voltage Range CMRR > 38 dB ±3.5 ±3.8 V
l TEXAS INSTRUMENTS
6
LMH6552
SNOSAX9J APRIL 2007REVISED APRIL 2016
www.ti.com
Product Folder Links: LMH6552
Submit Documentation Feedback Copyright © 2007–2016, Texas Instruments Incorporated
Electrical Characteristics: ±5 V (continued)
Unless otherwise specified, all limits are ensured for TA= 25°C, V+= +5 V, V=5 V, AV= 1, VCM = 0 V, RF= RG= 357 , RL
= 500 , for single ended in, differential out.(1)
PARAMETER TEST CONDITIONS MIN(2) TYP(3) MAX(2) UNIT
(5) Limit short circuit current in duration to no more than 10 seconds. See Power Dissipation for more details.
(6) Negative input current implies current flowing out of the device.
OUTPUT PERFORMANCE
Output Voltage Swing (3) Differential Output 14.8 15.4 VPP
IOUT Linear Output Current (3) VOUT = 0 V ±70 ±80 mA
ISC Short Circuit Current One Output Shorted to Ground VIN = 2 V
Single Ended (5) ±141 mA
Output Balance Error ΔVOUT Common Mode / ΔVOUT
Differential, ΔVOD = 1 V, f < 1 MHz –60 dB
MISCELLANEOUS PERFORMANCE
ZTOpen Loop Transimpedance Differential 108 dB
PSRR Power Supply Rejection Ratio DC, (V+- |V-|) = ±1 V 80 dB
ISSupply Current (3) RL=19 22.5 25
28 mA
Enable Voltage Threshold 3 V
Disable Voltage Threshold 2.0 V
Enable/Disable time 15 ns
ISD Disable Shutdown Current 500 600 μA
OUTPUT COMMON MODE CONTROL CIRCUIT
Common Mode Small Signal
Bandwidth VIN+= VIN= 0 400 MHz
Slew Rate VIN+= VIN= 0 607 V/μs
VOSCM Input Offset Voltage Common Mode, VID = 0, VCM = 0 1.5 ±16.5 mV
Input Bias Current (6) –3.2 ±8 µA
Voltage Range ±3.7 ±3.8 V
CMRR Measure VOD, VID = 0 V 80 dB
Input Resistance 200 k
Gain ΔVO,CM /ΔVCM 0.995 1.0 1.012 V/V
l TEXAS INSTRUMENTS
7
LMH6552
www.ti.com
SNOSAX9J APRIL 2007REVISED APRIL 2016
Product Folder Links: LMH6552
Submit Documentation FeedbackCopyright © 2007–2016, Texas Instruments Incorporated
(1) Electrical Table values apply only for factory testing conditions at the temperature indicated. Factory testing conditions result in very
limited self-heating of the device such that TJ= TA. No specification of parametric performance is indicated in the electrical tables under
conditions of internal self-heating where TJ> TA. See Overview for information on temperature de-rating of this device." Min/Max ratings
are based on product characterization and simulation. Individual parameters are tested as noted.
(2) Limits are 100% production tested at 25°C. Limits over the operating temperature range are ensured through correlation using Statistical
Quality Control (SQC) methods.
(3) Typical values represent the most likely parametric norm as determined at the time of characterization. Actual typical values can vary
over time and also depend on the application and configuration. The typical values are not tested and are not ensured on shipped
production material.
(4) IBoffset is referred to a differential output offset voltage by the following relationship: VOD(offset) = IBI*2RF.
(5) Limit short circuit current in duration to no more than 10 seconds. See Power Dissipation for more details.
6.6 Electrical Characteristics: ±2.5 V
Unless otherwise specified, all limits are ensured for TA= 25°C, V+= +2.5 V, V=2.5 V, AV= 1, VCM = 0 V, RF= RG=
357 , RL= 500 , for single ended in, differential out.(1)
PARAMETER TEST CONDITIONS MIN (2) TYP (3) MAX (2) UNIT
SSBW Small Signal 3-dB Bandwidth (2) VOUT = 0.2 VPP, AV= 1, RL= 1 k1100
MHz
VOUT = 0.2 VPP, AV= 1 800
VOUT = 0.2 VPP, AV= 2 740
VOUT = 0.2 VPP, AV= 4 660
VOUT = 0.2 VPP, AV= 8 498
LSBW Large Signal 3 dB Bandwidth VOUT = 2 VPP, AV= 1, RL= 1 k820
MHz
VOUT = 2 VPP, AV= 1 690
VOUT = 2 VPP, AV= 2 620
VOUT = 2 VPP, AV= 4 589
VOUT = 2 VPP, AV= 8 480
0.1 dB Bandwidth VOUT = 0.2 VPP, AV= 1 300 MHz
Slew Rate 2-V Step, AV= 1 2100 V/μs
Rise/Fall Time, 10% to 90% 2-V Step 700 ps
0.1% Settling Time 2-V Step 10 ns
Overdrive Recovery Time VIN = 0.7-V to 0-V Step, AV= 5 V/V 6 ns
DISTORTION AND NOISE RESPONSE
HD2 2nd Harmonic Distortion VOUT = 2 VPP, f = 20 MHz, RL= 800 -82 dBc
VOUT = 2 VPP, f = 70 MHz, RL= 800 -65
HD3 3rd Harmonic Distortion VOUT = 2 VPP, f = 20 MHz, RL= 800 -79 dBc
VOUT = 2 VPP, f = 70 MHz, RL= 800 -67
IMD3 Two-Tone Intermodulation f 70 MHz, Third-Order Products,
VOUT = 2-VPP Composite 77 dBc
Input Noise Voltage f 1 MHz 1.1 nV/Hz
Input Noise Current f 1 MHz 19.5 pA/Hz
Noise Figure (See Figure 46) 50-System, AV= 9, 10 MHz 10.2 dB
INPUT CHARACTERISTICS
IBI Input Bias Current (4) 54 90 µA
IBoffset Input Bias Current Differential
(3) VCM = 0 V, VID = 0 V, IBoffset = (IB- IB+)/2 2.3 18 μA
CMRR Common-Mode Rejection Ratio (3) DC, VCM = 0 V, VID = 0 V 75 dBc
RIN Input Resistance Differential 15
CIN Input Capacitance Differential 0.5 pF
CMVR Input Common Mode Range CMRR > 38 dB ±1.0 ±1.3 V
OUTPUT PERFORMANCE
Output Voltage Swing (3) Differential Output 5.6 6.0 VPP
IOUT Linear Output Current (3) VOUT = 0 V ±55 ±65 mA
ISC Short Circuit Current One Output Shorted to Ground, VIN = 2 V
Single Ended (5) ±131 mA
l TEXAS INSTRUMENTS
8
LMH6552
SNOSAX9J APRIL 2007REVISED APRIL 2016
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Product Folder Links: LMH6552
Submit Documentation Feedback Copyright © 2007–2016, Texas Instruments Incorporated
Electrical Characteristics: ±2.5 V (continued)
Unless otherwise specified, all limits are ensured for TA= 25°C, V+= +2.5 V, V=2.5 V, AV= 1, VCM = 0 V, RF= RG=
357 , RL= 500 , for single ended in, differential out.(1)
PARAMETER TEST CONDITIONS MIN (2) TYP (3) MAX (2) UNIT
(6) Negative input current implies current flowing out of the device.
Output Balance Error ΔVOUT Common Mode / ΔVOUT
Differential, ΔVOD = 1 V, f < 1 MHz 60 dB
MISCELLANEOUS PERFORMANCE
ZT Open Loop Transimpedance Differential 107 dB
PSRR Power Supply Rejection Ratio DC, ΔVS= ±1 V 80 dB
ISSupply Current (3) RL=17 20.4 24
27 mA
Enable Voltage Threshold 0.5 V
Disable Voltage Threshold –0.5 V
Enable/Disable Time 15 ns
ISD Disable Shutdown Current 500 600 µA
OUTPUT COMMON MODE CONTROL CIRCUIT
Common Mode Small Signal
Bandwidth VIN+= VIN= 0 310 MHz
Slew Rate VIN+= VIN= 0 430 V/μs
VOSCM Input Offset Voltage Common Mode, VID = 0, VCM = 0 1.65 ±15 mV
Input Bias Current (6) 2.9 µA
Voltage Range ±1.19 ±1.25 V
CMRR Measure VOD, VID = 0 V 80 dB
Input Resistance 200 k
Gain ΔVO,CM /ΔVCM 0.995 1.0 1.012 V/V
l TEXAS INSTRUMENTS
-9
-8
-7
-6
-5
-4
-3
-2
-1
0
1
2
3
1 10 100 10000
FREQUENCY (MHz)
NORMALIZED GAIN (dB)
1000
V+ = +2.5V
V- = -2.5V
RL = 500:
RF = 357:
VOD = 0.2 VPP
AV = 1 V/V
V+ = +5V
V- = -5V
RL = 500:
RF = 357:
DIFFERENTIAL INPUT
-9
-8
-7
-6
-5
-4
-3
-2
-1
0
1
2
3
1 10 100 10000
FREQUENCY (MHz)
NORMALIZED GAIN (dB)
1000
V+ = +2.5V
V- = -2.5V
RL = 1 k:
RF = 301:
VOD = 0.2 VPP
AV = 1 V/V
V+ = +5V
V- = -5V
RL = 1 k:
RF = 301:
DIFFERENTIAL INPUT
110 100 1000 10000
FREQUENCY (MHz)
-9
-8
-7
-6
-5
-4
-3
-2
-1
0
1
NORMALIZED GAIN (dB)
AV = 8, RF = 400:
VOUT = 0.2 VPP
SINGLE-ENDED INPUT
AV = 4
AV = 2
AV = 1
110 100 1000 10000
FREQUENCY (MHz)
-9
-8
-7
-6
-5
-4
-3
-2
-1
0
1
NORMALIZED GAIN (dB)
VOUT = 0.2 VPP
DIFFERENTIAL INPUT
AV = 8
AV = 4
AV = 1
AV = 2
9
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6.7 Typical Characteristics V+= +5 V, V=5 V
(TA= 25°C, RF= RG= 357 , RL= 500 , AV= 1, for single ended in, differential out, unless specified).
Figure 1. Frequency Response vs Gain Figure 2. Frequency Response vs Gain
Figure 3. Frequency Response vs VOUT Figure 4. Frequency Response vs VOUT
Figure 5. Frequency Response vs Supply Voltage Figure 6. Frequency Response vs Supply Voltage
l TEXAS INSTRUMENTS
0 5 10 15 20 25 30 35 40 45 50
-1.5
-1
-0.5
0
0.5
1
1.5
VOD (V)
TIME (ns)
V+ = +5
V- = -5V
RL = 500:
RF = 357:
05 10 15 20 25 30 35 40 45 50
-2.5
-2
-1.5
-1
-0.5
0
0.5
1
1.5
2
2.5
VOD (V)
TIME (ns)
V+ = +5V
V- = -5V
RL = 500:
RF = 357:
0 5 10 15 20 25 30 35 40 45 50
-0.8
-0.6
-0.4
-0.2
0
0.2
0.4
0.6
0.8
VOD (V)
TIME (ns)
V+ = +2.5V
V- = -2.5V
RL = 500:
RF = 357:
110000
FREQUENCY (MHz)
-9
-5
-2
2
NORMALIZED GAIN (dB)
1000
100
10
0
-4
-8
1
-1
-3
-6
-7
V+ = +5V
V- = -5V
AV = 1 V/V
VOUT = 2 VPP
RL = 1 k:
RF = 301:
RF = 357:
RF = 400:
DIFFERENTIAL INPUT
110 100 1000 10000
FREQUENCY (MHz)
-9
-8
-7
-6
-5
-4
-3
-2
-1
0
1
NORMALIZED GAIN (dB)
RL = 200:
RL = 1 k:
RL = 500:
RL = 800:
V+ = +5V
V- = -5V
AV = 1 V/V
RF = 357:
VOUT = 0.2 VPP
SINGLE-ENDED INPUT
110 100 1000 10000
FREQUENCY (MHz)
-9
-8
-7
-6
-5
-4
-3
-2
-1
0
1
NORMALIZED GAIN (dB)
RL = 200:
RL = 1 k:
RL = 500:
RL = 800:
V+ = +5V
V- = -5V
AV = 1 V/V
RF = 357:
VOUT = 2 VPP
SINGLE-ENDED INPUT
10
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Typical Characteristics V+= +5 V, V=5 V (continued)
(TA= 25°C, RF= RG= 357 , RL= 500 , AV= 1, for single ended in, differential out, unless specified).
Figure 7. Frequency Response vs Resistive Load Figure 8. Frequency Response vs Resistive Load
Figure 9. Frequency Response vs RFFigure 10. 1 VPP Pulse Response Single Ended Input
Figure 11. 2 VPP Pulse Response Single Ended Input Figure 12. Large Signal Pulse Response
l TEXAS INSTRUMENTS 4m ,5.) X\ ‘ RL = 5000 3 2v» m -60 3 1c : 20 MHz 5 E ,70 o HD3 5’ an E V V A 790 /' Hm v: 400 a 5 7 s 11 12 TOTAL supp” VOLTAGE M \
00.5 1 1.5 2 2.5 3
VOCM (V)
-100
-90
-80
-70
-60
-50
-40
DISTORTION (dBc)
V+ = +5V
V- = -5V
RL = 800:
VOUT = 2 VPP
fc = 20 MHz
HD2
HD3
00.5 1 1.5 2 2.5 3
VOCM (V)
-90
-80
-70
-60
-50
-40
DISTORTION (dBc)
HD2
HD3
V+ = +5V
V- = -5V
RL = 800:
VOUT = 2 VPP
fc = 75 MHz
HD2
HD3
35 7 9 11 12
-90
-80
-70
-60
-50
-20
DISTORTION (dBc)
TOTAL SUPPLY VOLTAGE (V)
-40
-30
RL = 800:
VOUT = 2 VPP
fc = 75 MHz
FREQUENCY (MHz)
DISTORTION (dBc)
-50
-55
-60
-65
-70
-75
-80
-85
-90
-95
-100
-1051 25 50 75 100 125 150 175 200 225 250
HD2
HD3
V+ = +5V
V- = -5V
RL = 800Ö
VOD = 2 VPP
VOCM = 0V
0 5 10 15 20 25 30 35 40 45 50
-80
-60
-40
-20
0
20
40
60
80
COMMON MODE VOUT (mV)
TIME (ns)
V+ = +5V
V- = -5V
RL = 500:
RL = 357:
VOD = 2 VPP
11
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Typical Characteristics V+= +5 V, V=5 V (continued)
(TA= 25°C, RF= RG= 357 , RL= 500 , AV= 1, for single ended in, differential out, unless specified).
Figure 13. Output Common Mode Pulse Response Figure 14. Distortion vs Frequency Single Ended Input
Figure 15. Distortion vs Supply Voltage Figure 16. Distortion vs Supply Voltage
Figure 17. Distortion vs Output Common Mode Voltage Figure 18. Distortion vs Output Common Mode Voltage
l TEXAS INSTRUMENTS
0.01 1 100 1000
FREQUENCY (MHz)
0.0001
10
1000
|Z| (:)
10
0.1
100
0.001
0.1
1
0.01
V+ = +5V
V- = -5V
VIN = 0V
AV = 1 V/V
0.01 0.1 110 1000
FREQUENCY (MHz)
0.01
0.1
100
1000
|Z| (:)
100
1
10
V+ = +2.5V
V- = -2.5
VIN = 0V
AV = 1 V/V
120
0.01 11000
FREQUENCY (MHz)
40
70
MAGNITUDE, |Z| (dB :)
100
10
0.1
100
90
60
50
80
110
-180
-45
-90
-135
0
MAGNITUDE
PHASE
V+ = +5V
V- = -5V
PHASE (°)
120
0.01 11000
FREQUENCY (MHz)
40
70
MAGNITUDE, |Z| (dB :)
100
10
0.1
100
90
60
50
80
110
-180
-45
-90
-135
0
MAGNITUDE
PHASE
V+ = +2.5V
V- = -2.5V
PHASE (°)
4
0 -10 -20 -30 -40 -50 -60
2
2.2
2.4
2.6
2.8
3
3.2
3.4
3.6
3.8
MAXIMUM VOUT (V)
OUTPUT CURRENT (mA)
V+ = +5V
V- = -5V
RF = 357:
VIN = 3.8V SINGLE-ENDED INPUT
-2
0 10 20 30 40 50 60
-4
-3.8
-3.6
-3.4
-3.2
3
-2.8
-2.6
-2.4
-2.2
OUTPUT CURRENT (mA)
V+ = +5V
V- = -5V
RF = 357:
VIN = 3.8V SINGLE-ENDED
MINIMUM VOUT (V)
12
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Typical Characteristics V+= +5 V, V=5 V (continued)
(TA= 25°C, RF= RG= 357 , RL= 500 , AV= 1, for single ended in, differential out, unless specified).
Figure 19. Maximum VOUT vs IOUT Figure 20. Minimum VOUT vs IOUT
Figure 21. Open Loop Transimpedance Figure 22. Open Loop Transimpedance
Figure 23. Closed Loop Output Impedance Figure 24. Closed Loop Output Impedance
l TEXAS INSTRUMENTS
0.1 11000
FREQUENCY (MHz)
20
40
65
85
CMRR (dB)
100
10
75
55
30
25
35
45
50
60
70
80
AV = 2 V/V
RL = 500:
RF = 357:
VOUT = 1.0 VPP
11000
FREQUENCY (MHz)
-70
-50
-30
-10
BALANCE ERROR (dBc)
100
10
-20
-40
-60
-15
-25
-35
-45
-55
-65
V+ = +2.5V
V- = -2.5V
RL = 500:
RF = 357:
AV = 1 V/V
V+ = +5V
V- = -5V
0
40
100
PSRR (dBc DIFFERENTIAL)
80
60
20
90
70
50
30
10
11000
FREQUENCY (MHz)
100
10
0.1
+PSRR
-PSRR
V+ = +5V
V- = -5V
AV = 2 V/V
RL = 500:
VIN = 0V
0.1 1000
FREQUENCY (MHz)
0
-40
-70
-110
PSRR (dBc DIFFERENTIAL)
100
10
1
-90
-50
-10
-100
-80
-60
-30
-20
+PSRR
-PSRR
V+ = +2.5V
V- = -2.5V
AV = 2 V/V
RL = 500:
VIN = 0V
0 200 400 600 800 1000
-10
-8
-6
-4
-2
0
2
4
6
8
10
OUTPUT VOLTAGE (VOD)
TIME (ns)
V+ = +5V
V- = -5V
AV = 5 V/V
RF = 324:
RL = 200:-2
-1.6
-1.2
-0.8
-0.4
0
0.4
0.8
1.2
1.6
2
INPUT VOLTAGE (V)
INPUT
OUTPUT
0 200 400 600 800 1000
-4
-3
-2
-1
0
1
2
3
4
OUTPUT VOLTAGE (VOD)
TIME (ns)
-0.8
-0.6
-0.4
-0.2
0
0.2
0.4
0.6
0.8
INPUT VOLTAGE (V)
V+ = +2.5V
V- = -2.5V
AV = 5 V/V
RF = 324:
RL = 200:
INPUT
OUTPUT
13
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Typical Characteristics V+= +5 V, V=5 V (continued)
(TA= 25°C, RF= RG= 357 , RL= 500 , AV= 1, for single ended in, differential out, unless specified).
Figure 25. Overdrive Recovery Figure 26. Overdrive Recovery
Figure 27. PSRR Figure 28. PSRR
Figure 29. CMRR Figure 30. Balance Error
‘5‘ TEXAS INSTRUMENTS
10 100 1000
-300
-200
-100
0
100
200
300
400
PHASE (°)
FREQUENCY (MHz)
S11
S22
S12
S11
(SINGLE-ENDED INPUT) S21
V+ = +5V
V- = -5V
AV = 1 V/V
0 1 2 3 4 5 6 7
-110
-100
-90
-80
-70
-60
-50
-40
-30
-20
IMD 3 (dBc)
DIFFERENTIAL VOUT (VPP)
fc = 75 MHz (200 kHz SPACING)
SINGLE-ENDED INPUT
RL = 200:
RL = 800:
V+ = +5V
V- = -5V
RF = 357:
AV = 2 V/V
0.0001 0.01 1 100
FREQUENCY (MHz)
100.1
0.001
VOLTAGE NOISE (nV/
Hz)
NOISE VOLTAGE
INVERTING CURRENT
NOISE CURRENT
NON-INVERTING CURRENT
NOISE CURRENT
6
0
4
5
3
2
1
210
0
140
175
105
70
35
CURRENT NOISE (pA/
Hz)
10 100 1000
-80
-70
-60
-50
-40
-30
-20
-10
0
MAGNITUDE (dB)
FREQUENCY (MHz)
V+ = +5V
V- = -5V
AV = 1 V/V
S21 S22
S11
S12
S11
(SINGLE-ENDED
INPUT)
0 20 40 60 80 100 120 140 160 180 200
10
11
12
13
14
15
NOISE FIGURE (dB)
FREQUENCY (MHz)
V+ = +5V
V- = -5V
AV = 9 V/V
RF = 275:
50: SYSTEM
0 20 40 60 80 100 120 140 160 180 200
10
11
12
13
14
15
NOISE FIGURE (dB)
FREQUENCY (MHz)
V+ = +2.5V
V- = -2.5V
AV = 9 V/V
RF = 275:
50: SYSTEM
14
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Typical Characteristics V+= +5 V, V=5 V (continued)
(TA= 25°C, RF= RG= 357 , RL= 500 , AV= 1, for single ended in, differential out, unless specified).
Figure 31. Noise Figure Figure 32. Noise Figure
Figure 33. Input Noise vs Frequency Figure 34. Differential S-Parameter Magnitude vs Frequency
Figure 35. Differential S-Parameter Phase vs Frequency Figure 36. 3rd Order Intermodulation Products vs VOUT
l TEXAS INSTRUMENTS
0 1 2 3 4 5 6 7
-110
-100
-90
-80
-70
-60
-50
-40
-30
-20
IMD 3 (dBc)
DIFFERENTIAL VOUT (VPP)
fc = 75 MHz (200 kHz SPACING)
SINGLE-ENDED INPUT
RL = 200:
RL = 800:
V+ = +2.5V
V- = -2.5V
RF = 357:
AV = 2 V/V
50 60 70 80 90 100
-100
-95
-90
-85
-80
-75
-70
-65
IMD 3 (dBc)
CENTER FREQUENCY (MHz)
V+ = +2.5V
V- = -2.5V
V+ = +5V
V- = -5V
RL = 800:
RF = 360:
AV = +2
VOD = 2 VPP
SINGLE-ENDED INPUT
200 kHz SPACING
15
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Typical Characteristics V+= +5 V, V=5 V (continued)
(TA= 25°C, RF= RG= 357 , RL= 500 , AV= 1, for single ended in, differential out, unless specified).
Figure 37. 3rd Order Intermodulation Products vs VOUT Figure 38. 3rd Order Intermodulation Products
vs Center Frequency
l TEXAS INSTRUMENTS
V+
-IN
+
±
High-Aol
Differential I/O
Amplifier
+IN
2.5 k
2.5 k
+OUT
-OUT
+
±
+
±
Vcm
Error
Amplifier VCM
V+
VEN Buffer
V±
High
Impedance
Copyright © 2016, Texas Instruments Incorporated
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7 Detailed Description
7.1 Overview
The LMH6552 is a fully differential current feedback amplifier with integrated output common mode control,
designed to provide low distortion amplification to wide bandwidth differential signals. The common mode
feedback circuit sets the output common mode voltage independent of the input common mode, as well as
forcing the V+ and Voutputs to be equal in magnitude and opposite in phase, even when only one of the inputs
is driven as in single to differential conversion.
7.2 Functional Block Diagram
7.3 Feature Description
The proprietary current feedback architecture of the LMH6552 offers gain and bandwidth independence with
exceptional gain flatness and noise performance, even at high values of gain, simply with the appropriate choice
of RF1 and RF2. Generally, RF1 is set equal to RF2, and RG1 equal to RG2, so that the gain is set by the ratio
RF/RG. Matching of these resistors greatly affects CMRR, DC offset error, and output balance. A maximum of
0.1% tolerance resistors are recommended for optimal performance, and the amplifier is internally compensated
to operate with optimum gain flatness with RF value of 200 Ωdepending on PCB layout, and load resistance.
The output common mode voltage is set by the VCM pin with a fixed gain of 1 V/V. Drive this pin by a low
impedance reference and bypassed to ground with a 0.1-μF ceramic capacitor. Any unwanted signal coupling
into the VCM pin is passed along to the outputs, reducing the performance of the amplifier. The LMH6552 can be
configured to operate on a single 10V supply connected to V+ with V- grounded or configured for a split supply
operation with V+ = +5 V and V=5 V. Operation on a single 10-V supply, depending on gain, is limited by the
input common mode range; therefore, AC coupling may be required.
l TEXAS INSTRUMENTS
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7.4 Device Functional Modes
This wideband FDA requires external resistors for correct signal-path operation. When configured for the desired
input impedance and gain setting with these external resistors, the amplifier can be either on with the PD pin
asserted to a voltage greater than Vs– + 3.0 V, or turned off by asserting PD low. Disabling the amplifier shuts
off the quiescent current and stops correct amplifier operation. The signal path is still present for the source
signal through the external resistors. The Vocm control pin sets the output average voltage. Left open, Vocm
floats to an indeterminate voltage. Driving this high-impedance input with a voltage reference within its valid
range sets a target for the internal Vcm error amplifier.
8 Application and Implementation
NOTE
Information in the following applications sections is not part of the TI component
specification, and TI does not warrant its accuracy or completeness. TI’s customers are
responsible for determining suitability of components for their purposes. Customers should
validate and test their design implementation to confirm system functionality.
8.1 Application Information
The proprietary current feedback architecture of the LMH6552 offers gain and bandwidth independence with
exceptional gain flatness and noise performance, even at high values of gain, simply with the appropriate choice
of RF1 and RF2. Generally RF1 is set equal to RF2, and RG1 equal to RG2, so that the gain is set by the ratio RF/RG.
Matching of these resistors greatly affects CMRR, DC offset error, and output balance. A minimum of 0.1%
tolerance resistors are recommended for optimal performance, and the amplifier is internally compensated to
operate with optimum gain flatness with values of RFbetween 270 and 390 depending on package
selection, PCB layout, and load resistance.
The output common mode voltage is set by the VCM pin with a fixed gain of 1 V/V. This pin must be driven by a
low impedance reference and must be bypassed to ground with a 0.1 µF ceramic capacitor. Any unwanted signal
coupling into the VCM pin is passed along to the outputs, reducing the performance of the amplifier. This pin must
not be left floating.
The LMH6552 can be operated on a supply range as either a single 5V supply or as a split +5 V and 5 V.
Operation on a single 5-V supply, depending on gain, is limited by the input common mode range; therefore, AC
coupling may be required. For example, in a DC coupled input application on a single 5-V supply, with a VCM of
1.5 V, the input common voltage at a gain of 1 is 0.75 V, which is outside the minimum 1.2-V to 3.8-V input
common mode range of the amplifier. The minimum VCM for this application must be greater than 2.5 V
depending on output signal swing. Alternatively, AC coupling of the inputs in this example results in equal input
and output common mode voltages, so a 1.5 V VCM would be achievable. Split supplies allow much less
restricted AC and DC coupled operation with optimum distortion performance.
The LMH6552 is equipped with an ENABLE pin to reduce power consumption when not in use. The ENABLE
pin, when not driven, floats high (on). When the ENABLE pin is pulled low the amplifier is disabled and the
amplifier output stage goes into a high impedance state so the feedback and gain set resistors determine the
output impedance of the circuit. For this reason input to output isolation is poor in the disabled state and the part
is not recommended in multiplexed applications where outputs are all tied together.
8.2 Typical Applications
8.2.1 Typical Fully Differential Application
In many applications, it is required to drive a differential input ADC from a single ended source. Traditionally,
transformers have been used to provide single to differential conversion, but these are inherently bandpass by
nature and cannot be used for DC coupled applications. The LMH6552 provides excellent performance as a
single-to-differential converter down to DC. Figure 45 illustrates a typical application circuit where an LMH6552 is
used to produce a differential signal from a single ended source.
l TEXAS INSTRUMENTS
VS
RG
RG
VCM RLVO
RF
RF
CL
RO
RO
ENABLE
a
+
-
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Typical Applications (continued)
Figure 39. Typical Fully Differential Application Schematic
8.2.1.1 Design Requirements
One typical application for the LMH6552 is to drive an ADC. The following design is a single ended to differential
circuit with an input impedance of 50 Ωand an output impedance of 100 Ω. The VCM voltage of the amplifier
needs to be set to the same voltage as the ADC reference voltage which is typically 1.2 V. Figure 45 illustrates
the design equations required to set the external resistor values. This design also requires a gain of 1 and -74
dBc THD at 70 MHz.
8.2.1.2 Detailed Design Procedure
To match the input impedance of the circuit in Figure 45 to a specified source resistance, RS, requires that RT ||
RIN = RS. The equations governing RIN and AV for single-to-differential operation are also provided in
Figure 45. These equations, along with the source matching condition, must be solved iteratively to achieve the
desired gain with the proper input termination. Component values for several common gain configurations in a
50-Ωenvironment are given in Table 1. Gain Component Values for 50-ΩSystem WSON Package. Typically
RS=50 Ωand RM=RS||RT.
8.2.1.2.1 WSON Package
Due to its size and lower parasitics, the WSON requires the lower optimum value of 275 for RF. This gives a
flat frequency response with minimal peaking. With a lower RFvalue the WSON package has a reduction in
noise compared to the SOIC with its optimum RF= 360 .
8.2.1.2.2 Fully Differential Operation
The LMH6552 performs best in a fully differential configuration. The circuit illustrated in Figure 39 is a typical fully
differential application circuit as might be used to drive an analog to digital converter (ADC). In this circuit the
closed loop gain AV= VOUT/ VIN = RF/RG, where the feedback is symmetric. The series output resistors, RO, are
optional and help keep the amplifier stable when presented with a capacitive load. Refer to Driving Capacitive
Loads for details.
When driven from a differential source, the LMH6552 provides low distortion, excellent balance, and common
mode rejection. This is true provided the resistors RF, RGand ROare well matched and strict symmetry is
observed in board layout. With an intrinsic device CMRR of 80 dB, using 0.1% resistors gives a worst case
CMRR of around 60 dB for most circuits.
The circuit configuration illustrated in Figure 40 was used to measure differential S parameters in a 50-
environment at a gain of 1 V/V. Refer to Figure 34 and Figure 35 in the Typical Characteristics for measurement
results.
l TEXAS INSTRUMENTS 357 ~—w»— V 1- m o—w— —w»— 3570 357 35m
VSVCM RL
357:
50:
ENABLE
a+
-
357:
348:
348:
50:
26.4:
56.2:
RS = 50:
VSVCM RL
357:
50:
ENABLE
a
+
-
357:
357:
357:
50:
58:
58:
RS = 50:
RS = 50:
19
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Typical Applications (continued)
Figure 40. Differential S-Parameter Test Circuit
Table 1. Gain Component Values for 50System WSON Package
Gain RFRGRTRM
0 dB 2752555926.7
6 dB 27512768.128.7
12 dB 27554.910734
Figure 41. Single Ended Input S-Parameter Test Circuit (50System)
The circuit shown in Figure 41 was used to measure S-parameters for a single-to-differential configuration.
Figure 34 and Figure 35 in Typical Characteristics are taken using the recommended component values for 0 dB
gain.
8.2.1.2.3 Driving Capacitive Loads
As noted previously, capacitive loads must be isolated from the amplifier output with small valued resistors. This
is particularly the case when the load has a resistive component that is 500 or higher. A typical ADC has
capacitive components of around 10 pF and the resistive component could be 1000 or higher. If driving a
transmission line, such as 50coaxial or 100twisted pair, using matching resistors is sufficient to isolate any
subsequent capacitance.
8.2.1.2.3.1 Balanced Cable Driver
With up to 15 VPP differential output voltage swing and 80 mA of linear drive current the LMH6552 makes an
excellent cable driver as illustrated in Figure 42. The LMH6552 is also suitable for driving differential cables from
a single ended source.
l TEXAS INSTRUMENTS
110 100 1000
FREQUENCY (MHz)
-9
-8
-7
-6
-5
-4
-3
-2
-1
0
1
NORMALIZED GAIN (dB)
CL = 82 pF, RO = 16:
CL = 39 pF, RO = 21:
CL = 15 pF, RO = 24:
CL = 5.6 pF, RO = 23:
VOD = 200 mVPP
AV = 1
LOAD = (CL || 1 k:) IN
SERIES WITH 2 ROUTS
VSVCM
ENABLE
100:
TWISTED PAIR
50:
2 VPP
357:
169:
AV = 2 V/V
50:
a
+
-
357:
169:
27.6:
61.8:
RS = 50:
20
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Figure 42. Fully Differential Cable Driver
8.2.1.3 Application Curves
Many application circuits have capacitive loading. As shown in Figure 43 amplifier bandwidth is reduced with
increasing capacitive load, so parasitic capacitance must be strictly limited.
In order to ensure stability resistance must be added between the capacitive load and the amplifier output pins.
The value of the resistor is dependent on the amount of capacitive load as shown in Figure 44. This resistive
value is a suggestion. System testing is required to determine the optimal value. Using a smaller resistor retains
more system bandwidth at the expense of overshoot and ringing, and larger values of resistance reduce
overshoot but also reduce system bandwidth.
Figure 43. Frequency Response vs Capacitive Load Figure 44. Suggested ROUT vs Capacitive Load
l TEXAS INSTRUMENTS
RG
RG
RF
RF
RO
+
-RO
LMH6552
IN-
IN+
ADC
V+
V-
VO
+
-
RT
RS
RM
VS
AV, RIN
a
AV = 2(1 - E1)
E1 + E2
¨
¨
©
§
¨
¨
©
§
RIN = 2RG + RM (1-E2)
1 + E2
¨
¨
©
§
¨
¨
©
§
E2 =
RG + RM
RG + RF + RM
¨
¨
©
§
¨
¨
©
§
¨
¨
©
§
E1 =
RG
RG + RF
¨
¨
©
§
RS=RT || RIN
RM=RT || RS
+
-
VCM
Copyright © 2016, Texas Instruments Incorporated
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8.2.2 Single-Ended Input to Differential Output Operation
In many applications, it is required to drive a differential input ADC from a single-ended source. Traditionally,
transformers have been used to provide single to differential conversion, but these are inherently bandpass by
nature and cannot be used for DC coupled applications. The LMH6552 provides excellent performance as a
single-to-differential converter down to DC. Figure 45 shows a typical application circuit where an LMH6552 is
used to produce a differential signal from a single-ended source.
Figure 45. Single-Ended Input with Differential Output
When using the LMH6552 in single-to-differential mode, the complementary output is forced to a phase inverted
replica of the driven output by the common mode feedback circuit as opposed to being driven by its own
complimentary input. Consequently, as the driven input changes, the common mode feedback action results in a
varying common mode voltage at the amplifier's inputs, proportional to the driving signal. Due to the non-ideal
common mode rejection of the amplifier's input stage, a small common mode signal appears at the outputs which
is superimposed on the differential output signal. The ratio of the change in output common mode voltage to
output differential voltage is commonly referred to as output balance error. The output balance error response of
the LMH6552 over frequency is shown in the Typical Characteristics.
To match the input impedance of the circuit in Figure 45 to a specified source resistance, RS, requires that RT||
RIN = RS. The equations governing RIN and AVfor single-to-differential operation are also provided in Figure 45.
These equations, along with the source matching condition, must be solved iteratively to achieve the desired gain
with the proper input termination. Component values for several common gain configurations in a 50-
environment are given in Table 1. Typically RS=50and RM=RS||RT.
8.2.3 Single Supply Operation
Single supply operation is possible on supplies from 5 V to 10 V; however, as discussed earlier, AC input
coupling is recommended for low supplies such as 5 V due to input common mode limitations. An example of an
AC coupled, single supply, single-to-differential circuit is illustrated in Figure 46. Note that when AC coupling,
both inputs need to be AC coupled irrespective of single-to-differential or differential-to-differential configuration.
For higher supply voltages DC coupling of the inputs may be possible provided that the output common mode
DC level is set high enough so that the amplifier's inputs and outputs are within their specified operating ranges.
l TEXAS INSTRUMENTS
169:
+
-
LMH6552
V+
V-
2.2 pF
VREF
169:
-
+
125:
125:
357:
357:
ADC12DL080
12-Bit
80 MSPS
CIN
~ 7- 8 pF
61.8:
50:
Single-Ended
AC-coupled
Source
61.8:
49.9:
0.1 PF
Copyright © 2016, Texas Instruments Incorporated
RG
RG
VCM RLVO
RF
RF
CL
RO
RO
ENABLE
+
-
VSa
VO1
VO2
VI2
VI1
RM
RT
RS
VICM = VOCM
VICM = VI1 + VI2
2
*VCM = VO1 + VO2
2
*BY DESIGN
Copyright © 2016, Texas Instruments Incorporated
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Figure 46. AC Coupled for Single Supply Operation
8.2.4 Split Supply Operation
For optimum performance, split supply operation is recommended using +5 V and 5 V supplies; however,
operation is possible on split supplies as low as +2.25 V and 2.25 V and as high as +6 V and 6 V. Provided
the total supply voltage does not exceed the 4.5-V to 12-V operating specification, non-symmetric supply
operation is also possible and in some cases advantageous. For example, if a 5-V DC coupled operation is
required for low power dissipation but the amplifier input common mode range prevents this operation, it is still
possible with split supplies of (V+) and (V). Where (V+) - (V) = 5V and V+and Vare selected to center the
amplifier input common mode range to suit the application.
Figure 47. Split Supply
8.2.5 Output Noise Performance and Measurement
Unlike differential amplifiers based on voltage feedback architectures, noise sources internal to the LMH6552
refer to the inputs largely as current sources, hence the low input referred voltage noise and relatively higher
input referred current noise. The output noise is therefore more strongly coupled to the value of the feedback
resistor and not to the closed loop gain, as would be the case with a voltage feedback differential amplifier. This
allows operation of the LMH6552 at much higher gain without incurring a substantial noise performance penalty,
simply by choosing a suitable feedback resistor.
l TEXAS INSTRUMENTS 275 357
169:
+
-
LMH6552
V+
V-
2.2 pF
VREF
169:
-
+
125:
125:
357:
357:
ADC12DL080
12-Bit
80 MSPS
CIN
~ 7- 8 pF
61.8:
50:
Single-Ended
AC-coupled
Source
61.8:
49.9:
0.1 PF
Copyright © 2016, Texas Instruments Incorporated
10:
275:
+
-
LMH6552
V+
V-
VO
+
-
VS
275:
10:
50:
RS = 50:
VCM 50:
2:1 (TURNS)
AV = 9 V/V
1 PF
1 PF
a
Copyright © 2016, Texas Instruments Incorporated
23
LMH6552
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Submit Documentation FeedbackCopyright © 2007–2016, Texas Instruments Incorporated
Figure 48 shows a circuit configuration used to measure noise figure for the LMH6552 in a 50-system. An RF
value of 275 is chosen for the SOIC package to minimize output noise and simultaneously allows both high
gain (9 V/V) and proper 50-input termination. Refer to Single-Ended Input to Differential Output Operation for
calculation of resistor and gain values. Noise figure values at various frequencies are shown Figure 31 in the
Typical Characteristics.
Figure 48. Noise Figure Circuit Configuration
8.2.6 Driving Analog to Digital Converters
Analog-to-digital converters present challenging load conditions. They typically have high impedance inputs with
large and often variable capacitive components. As well, there are usually current spikes associated with
switched capacitor or sample and hold circuits. Figure 49 shows a combination circuit of the LMH6552 driving the
ADC12DL080. The two 125-resistors serve to isolate the capacitive loading of the ADC from the amplifier and
ensure stability. In addition, the resistors, along with a 2.2-pF capacitor across the outputs (in parallel with the
ADC input capacitance), form a low pass anti-aliasing filter with a pole frequency of about 60 MHz. For switched
capacitor input ADCs, the input capacitance varies based on the clock cycle, as the ADC switches between the
sample and hold mode. See your particular ADC's datasheet for details.
Figure 49. Driving a 12-Bit ADC
Figure 50 illustrates the SFDR and SNR performance vs frequency for the LMH6552 and ADC12DL080
combination circuit with the ADC input signal level at 1 dBFS. The ADC12DL080 is a dual 12-bit ADC with
maximum sampling rate of 80 MSPS. The amplifier is configured to provide a gain of 2 V/V in single to
differential mode. An external band-pass filter is inserted in series between the input signal source and the
amplifier to reduce harmonics and noise from the signal generator. In order to properly match the input
impedance seen at the LMH6552 amplifier inputs, RMis chosen to match ZS|| RTfor proper input balance.
l TEXAS INSTRUMENTS 12752 274 :2
127:
+
-
LMH6552
V+
V-
22 pF
VREF
127:
-
+
100:
100:
274:
274:
ADC14DS105
14-Bit
105
MSPS
620 nH
620 nH
49.9:
68.1:
68.1:
0.1 PF
50:
Single-Ended
AC-coupled
Source
Copyright © 2016, Texas Instruments Incorporated
05 10 15 20 25 30 35 40
INPUT FREQUENCY (MHz)
50
55
60
65
70
75
80
85
90
(dB)
SFDR (dBc)
SNR (dBFs)
24
LMH6552
SNOSAX9J APRIL 2007REVISED APRIL 2016
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Product Folder Links: LMH6552
Submit Documentation Feedback Copyright © 2007–2016, Texas Instruments Incorporated
Figure 50. LMH6552/ADC12DL080 SFDR and SNR Performance vs. Frequency
Figure 51 shows a combination circuit of the LMH6552 driving the ADC14DS105. The ADC14DS105 is a dual
channel 14-bit ADC with a sampling rate of 105 MSPS. The circuit in Figure 51 has a 2nd order low-pass LC
filter formed by the 620 nH inductor along with the 22-pF capacitor across the differential outputs of the
LMH6552. The filter has a pole frequency of about 50 MHz. Figure 52 shows the combined SFDR and SNR
performance over frequency with a 1 dBFs input signal and a sampling rate of 1000 MSPS.
Figure 51. Driving a 14-bit ADC
The amplifier is configured to provide a gain of 2 V/V in a single-to-differential mode. The LMH6552 common
mode voltage is set by the ADC14DS105. Circuit testing is the same as described for the LMH6552 and
ADC12DL080 combination circuit. The 0.1-µF capacitor, in series with the 49.9-resistor, is inserted to ground
across the 68.1-resistor to balance the amplifier inputs.
l TEXAS INSTRUMENTS
0 5 10 15 20 25 30 35 40
50
100
(dB)
INPUT FREQUENCY (MHz)
55
60
65
70
75
80
85
90
95 SFDR (dBc)
SNR (dBFs)
25
LMH6552
www.ti.com
SNOSAX9J APRIL 2007REVISED APRIL 2016
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Submit Documentation FeedbackCopyright © 2007–2016, Texas Instruments Incorporated
Figure 52. LMH6552/ADC14DS105 SFDR and SNR Performance vs. Frequency
The amplifier and ADC must be located as close as possible. Both devices require that the filter components be
in close proximity to them. The amplifier needs to have minimal parasitic loading on the output traces and the
ADC is sensitive to high frequency noise that may couple in on its input lines. Some high performance ADCs
have an input stage that has a bandwidth of several times its sample rate. The sampling process results in all
input signals presented to the input stage mixing down into the first Nyquist zone (DC to Fs/2).
The LMH6552 is capable of driving a variety of Texas Instruments Analog-to-Digital Converters. This is shown in
Table 2, which offers a list of possible signal path ADC and amplifier combinations. The use of the LMH6552 to
drive an ADC is determined by the application and the desired sampling process (Nyquist operation, sub-
sampling or over-sampling). See application note AN-236 for more details on the sampling processes and
application note AN-1393 'Using High Speed Differential Amplifiers to Drive ADCs. For more information
regarding a particular ADC, refer to the particular ADC datasheet for details.
Table 2. Differential Input ADCs Compatible With LMH6552 Driver
Product Number Max Sampling Rate (MSPS) Resolution Channels
ADC1173 15 8 SINGLE
ADC1175 20 8 SINGLE
ADC08351 42 8 SINGLE
ADC1175-50 50 8 SINGLE
ADC08060 60 8 SINGLE
ADC08L060 60 8 SINGLE
ADC08100 100 8 SINGLE
ADC08200 200 8 SINGLE
ADC08500 500 8 SINGLE
ADC081000 1000 8 SINGLE
ADC08D1000 1000 8 DUAL
ADC10321 20 10 SINGLE
ADC10D020 20 10 DUAL
ADC10030 27 10 SINGLE
ADC10040 40 10 DUAL
ADC10065 65 10 SINGLE
ADC10DL065 65 10 DUAL
ADC10080 80 10 SINGLE
ADC11DL066 66 11 DUAL
ADC11L066 66 11 SINGLE
ADC11C125 125 11 SINGLE
l TEXAS INSTRUMENTS
26
LMH6552
SNOSAX9J APRIL 2007REVISED APRIL 2016
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Product Folder Links: LMH6552
Submit Documentation Feedback Copyright © 2007–2016, Texas Instruments Incorporated
Table 2. Differential Input ADCs Compatible With LMH6552 Driver (continued)
Product Number Max Sampling Rate (MSPS) Resolution Channels
ADC11C170 170 11 SINGLE
ADC12010 10 12 SINGLE
ADC12020 20 12 SINGLE
ADC12040 40 12 SINGLE
ADC12D040 40 12 DUAL
ADC12DL040 40 12 DUAL
ADC12DL065 65 12 DUAL
ADC12DL066 66 12 DUAL
ADC12L063 63 12 SINGLE
ADC12C080 80 12 SINGLE
ADC12DS080 80 12 DUAL
ADC12L080 80 12 SINGLE
ADC12C105 105 12 SINGLE
ADC12DS105 105 12 DUAL
ADC12C170 170 12 SINGLE
ADC14L020 20 14 SINGLE
ADC14L040 40 14 SINGLE
ADC14C080 80 14 SINGLE
ADC14DS080 80 14 DUAL
ADC14C105 105 14 SINGLE
ADC14DS105 105 14 DUAL
ADC14155 155 14 SINGLE
9 Power Supply Recommendations
The LMH6552 can be used with any combination of positive and negative power supplies as long as the
combined supply voltage is between 4.5 V and 12 V. The LMH6552 provides best performance when the output
voltage is set at the mid supply voltage, and when the total supply voltage is between 9 V and 12 V. When
selecting a supply voltage that is less than 9 V, it is important to consider both the input common mode voltage
range as well as the output voltage range.
Power supply bypassing as shown in Power Supply Bypassing is important and power supply regulation must be
within 5% or better using a supply voltage near the edges of the operating range.
9.1 Power Supply Bypassing
The LMH6552 requires supply bypassing capacitors as illustrated in Figure 53 and Figure 54. The 0.01-µF and
0.1-µF capacitors must be leadless SMT ceramic capacitors and must be no more than 3 mm from the supply
pins. These capacitors must be star routed with a dedicated ground return plane or trace for best harmonic
distortion performance. A small capacitor, ~0.01 µF, placed across the supply rails, and as close to the chip's
supply pins as possible, can further improve HD2 performance. Thin traces or small vias reduce the
effectiveness of bypass capacitors. Also shown in both figures is a capacitor from the VCM and ENABLE pins to
ground. These inputs are high impedance and can provide a coupling path into the amplifier for external noise
sources, possibly resulting in loss of dynamic range, degraded CMRR, degraded balance and higher distortion.
l TEXAS INSTRUMENTS
VCM
V+
10 PF
0.1 PF
+
-
0.1 PF0.01 PF
0.01 PF
ENABLE
VCM 0.01 PF
V+
V-0.1 PF
0.1 PF
10 PF
10 PF
0.1 PF
+
-
0.1 PF
ENABLE
27
LMH6552
www.ti.com
SNOSAX9J APRIL 2007REVISED APRIL 2016
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Submit Documentation FeedbackCopyright © 2007–2016, Texas Instruments Incorporated
Power Supply Bypassing (continued)
Figure 53. Split Supply Bypassing Capacitors
Figure 54. Single Supply Bypassing Capacitors
10 Layout
10.1 Layout Guidelines
The LMH6552 is a very high performance amplifier. In order to get maximum benefit from the differential circuit
architecture board layout and component selection is very critical. The circuit board must have a low inductance
ground plane and well bypassed broad supply lines. External components must be leadless surface mount types.
The feedback network and output matching resistors must be composed of short traces and precision resistors
(0.1%). The output matching resistors must be placed within 3 or 4 mm of the amplifier as must the supply
bypass capacitors. Refer to Power Supply Bypassing for recommendations on bypass circuit layout. Evaluation
boards are available free of charge through the product folder on ti.com.
By design, the LMH6552 is relatively insensitive to parasitic capacitance at its inputs. Nonetheless, ground and
power plane metal must be removed from beneath the amplifier and from beneath RFand RGfor best
performance at high frequency.
With any differential signal path, symmetry is very important. Even small amounts of asymmetry can contribute to
distortion and balance errors.
% TEXAS INSTRUMENTS Dunn Termination Resistol T1
28
LMH6552
SNOSAX9J APRIL 2007REVISED APRIL 2016
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10.2 Layout Example
Figure 55. Layout Schematic
l TEXAS INSTRUMENTS
29
LMH6552
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10.3 Thermal Considerations
The WSON package is designed for enhanced thermal performance and features an exposed die attach pad
(DAP) at the bottom center of the package that creates a direct path to the PCB for maximum power dissipation.
The DAP is floating and is not electrically connected to internal circuitry. Compared to the traditional leaded
packages where the die attach pad is embedded inside the molding compound, the WSON reduces one layer in
the thermal path.
The thermal advantage of the WSON package is fully realized only when the exposed die attach pad is soldered
down to a thermal land on the PCB board with thermal vias planted underneath the thermal land. The thermal
land can be connected to any power or ground plane within the allowable supply voltage range of the device.
Based on thermal analysis of the WSON package, the junction-to-ambient thermal resistance (θJA) can be
improved by a factor of two when the die attach pad of the WSON package is soldered directly onto the PCB
with thermal land and thermal vias are 1.27 mm and 0.33 mm respectively. Typical copper via barrel plating is 1
oz, although thicker copper may be used to further improve thermal performance.
For more information on board layout techniques, refer to Application Note 1187 Leadless Lead Frame Package
(LLP). This application note also discusses package handling, solder stencil and the assembly process.
10.4 Power Dissipation
The LMH6552 is optimized for maximum speed and performance in the small form factor of the standard SOIC
package, and is essentially a dual channel amplifier. To ensure maximum output drive and highest performance,
thermal shutdown is not provided. Therefore, it is of utmost importance to make sure that the TJMAXof 150°C is
never exceeded due to the overall power dissipation.
Follow these steps to determine the maximum power dissipation for the LMH6552:
1. Calculate the quiescent (no-load) power:
PAMP = ICC* (VS)
where
• VS= V+- V. (Be sure to include any current through the feedback network if VOCM is not mid-rail.) (1)
2. Calculate the RMS power dissipated in each of the output stages:
PD(rms) = rms ((VS- V+OUT) * I+OUT) + rms ((VSVOUT) * IOUT)
where
• VOUT and IOUT are the voltage and the current measured at the output pins of the differential amplifier as if they
were single ended amplifiers and VSis the total supply voltage (2)
3. Calculate the total RMS power:
PT= PAMP + PD(3)
The maximum power that the LMH6552 package can dissipate at a given temperature can be derived with the
following equation:
PMAX = (150° – TAMB)/ θJA
where
• TAMB = Ambient temperature (°C)
θJA = Thermal resistance, from junction to ambient, for a given package (°C/W)
For the SOIC package θJA is 150°C/W
For WSON package θJA is 58°C/W (4)
NOTE
If VCM is not 0V then there is quiescent current flowing in the feedback network. This
current must be included in the thermal calculations and added into the quiescent power
dissipation of the amplifier.
l TEXAS INSTRUMENTS
30
LMH6552
SNOSAX9J APRIL 2007REVISED APRIL 2016
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Product Folder Links: LMH6552
Submit Documentation Feedback Copyright © 2007–2016, Texas Instruments Incorporated
10.5 ESD Protection
The LMH6552 is protected against electrostatic discharge (ESD) on all pins. The LMH6552 can survive 2000 V
Human Body model and 200 V Machine model events. Under normal operation the ESD diodes have no affect
on circuit performance. There are occasions, however, when the ESD diodes are evident. If the LMH6552 is
driven by a large signal when the device is powered down the ESD diodes conduct. The current that flows
through the ESD diodes either exits the chip through the supply pins or flows through the device, hence a chip
can be powered up with a large signal applied to the input pins. Using the shutdown mode is one way to
conserve power and still prevent unexpected operation.
l TEXAS INSTRUMENTS
31
LMH6552
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Submit Documentation FeedbackCopyright © 2007–2016, Texas Instruments Incorporated
11 Device and Documentation Support
11.1 Device Support
11.1.1 Third-Party Products Disclaimer
TI'S PUBLICATION OF INFORMATION REGARDING THIRD-PARTY PRODUCTS OR SERVICES DOES NOT
CONSTITUTE AN ENDORSEMENT REGARDING THE SUITABILITY OF SUCH PRODUCTS OR SERVICES
OR A WARRANTY, REPRESENTATION OR ENDORSEMENT OF SUCH PRODUCTS OR SERVICES, EITHER
ALONE OR IN COMBINATION WITH ANY TI PRODUCT OR SERVICE.
11.2 Documentation Support
11.2.1 Related Documentation
For related documentation see the following:
Leadless Lead Frame Package (LLP), SNOA401
11.2.1.1 Evaluation Board
See the LMH6552 Product Folder for evaluation board availability and ordering information.
11.3 Community Resources
The following links connect to TI community resources. Linked contents are provided "AS IS" by the respective
contributors. They do not constitute TI specifications and do not necessarily reflect TI's views; see TI's Terms of
Use.
TI E2E™ Online Community TI's Engineer-to-Engineer (E2E) Community. Created to foster collaboration
among engineers. At e2e.ti.com, you can ask questions, share knowledge, explore ideas and help
solve problems with fellow engineers.
Design Support TI's Design Support Quickly find helpful E2E forums along with design support tools and
contact information for technical support.
11.4 Trademarks
E2E is a trademark of Texas Instruments.
All other trademarks are the property of their respective owners.
11.5 Electrostatic Discharge Caution
These devices have limited built-in ESD protection. The leads should be shorted together or the device placed in conductive foam
during storage or handling to prevent electrostatic damage to the MOS gates.
11.6 Glossary
SLYZ022 TI Glossary.
This glossary lists and explains terms, acronyms, and definitions.
12 Mechanical, Packaging, and Orderable Information
The following pages include mechanical, packaging, and orderable information. This information is the most
current data available for the designated devices. This data is subject to change without notice and revision of
this document. For browser-based versions of this data sheet, refer to the left-hand navigation.
I TEXAS INSTRUMENTS Samples Samples Samples
PACKAGE OPTION ADDENDUM
www.ti.com 10-Dec-2020
Addendum-Page 1
PACKAGING INFORMATION
Orderable Device Status
(1)
Package Type Package
Drawing Pins Package
Qty Eco Plan
(2)
Lead finish/
Ball material
(6)
MSL Peak Temp
(3)
Op Temp (°C) Device Marking
(4/5)
Samples
LMH6552MA/NOPB ACTIVE SOIC D 8 95 RoHS & Green SN Level-1-260C-UNLIM -40 to 85 LMH65
52MA
LMH6552MAX/NOPB ACTIVE SOIC D 8 2500 RoHS & Green SN Level-1-260C-UNLIM -40 to 85 LMH65
52MA
LMH6552SD/NOPB ACTIVE WSON NGS 8 1000 RoHS & Green SN Level-1-260C-UNLIM -40 to 85 6552
(1) The marketing status values are defined as follows:
ACTIVE: Product device recommended for new designs.
LIFEBUY: TI has announced that the device will be discontinued, and a lifetime-buy period is in effect.
NRND: Not recommended for new designs. Device is in production to support existing customers, but TI does not recommend using this part in a new design.
PREVIEW: Device has been announced but is not in production. Samples may or may not be available.
OBSOLETE: TI has discontinued the production of the device.
(2) RoHS: TI defines "RoHS" to mean semiconductor products that are compliant with the current EU RoHS requirements for all 10 RoHS substances, including the requirement that RoHS substance
do not exceed 0.1% by weight in homogeneous materials. Where designed to be soldered at high temperatures, "RoHS" products are suitable for use in specified lead-free processes. TI may
reference these types of products as "Pb-Free".
RoHS Exempt: TI defines "RoHS Exempt" to mean products that contain lead but are compliant with EU RoHS pursuant to a specific EU RoHS exemption.
Green: TI defines "Green" to mean the content of Chlorine (Cl) and Bromine (Br) based flame retardants meet JS709B low halogen requirements of <=1000ppm threshold. Antimony trioxide based
flame retardants must also meet the <=1000ppm threshold requirement.
(3) MSL, Peak Temp. - The Moisture Sensitivity Level rating according to the JEDEC industry standard classifications, and peak solder temperature.
(4) There may be additional marking, which relates to the logo, the lot trace code information, or the environmental category on the device.
(5) Multiple Device Markings will be inside parentheses. Only one Device Marking contained in parentheses and separated by a "~" will appear on a device. If a line is indented then it is a continuation
of the previous line and the two combined represent the entire Device Marking for that device.
(6) Lead finish/Ball material - Orderable Devices may have multiple material finish options. Finish options are separated by a vertical ruled line. Lead finish/Ball material values may wrap to two
lines if the finish value exceeds the maximum column width.
Important Information and Disclaimer:The information provided on this page represents TI's knowledge and belief as of the date that it is provided. TI bases its knowledge and belief on information
provided by third parties, and makes no representation or warranty as to the accuracy of such information. Efforts are underway to better integrate information from third parties. TI has taken and
continues to take reasonable steps to provide representative and accurate information but may not have conducted destructive testing or chemical analysis on incoming materials and chemicals.
TI and TI suppliers consider certain information to be proprietary, and thus CAS numbers and other limited information may not be available for release.
I TEXAS INSTRUMENTS
PACKAGE OPTION ADDENDUM
www.ti.com 10-Dec-2020
Addendum-Page 2
In no event shall TI's liability arising out of such information exceed the total purchase price of the TI part(s) at issue in this document sold by TI to Customer on an annual basis.
l TEXAS INSTRUMENTS REEL DIMENSIONS TAPE DIMENSIONS ’ I+K0 '«PI» Reel Diame|er AD Dimension deSIgned Io accommodate me componem wIdIh E0 Dimension deSIgned Io eecommodaIe me componenI Iengm KO Dlmenslun desIgned to accommodate me componem Ihlckness 7 w OvereII wmm OHhe earner cape i p1 Pitch between successwe cavIIy cemers f T Reel Width (W1) QUADRANT ASSIGNMENTS FOR PIN 1 ORIENTATION IN TAPE O O O D O O D O SprockeIHoles ,,,,,,,,,,, ‘ User Direcllon 0' Feed Pockel Quadrams
TAPE AND REEL INFORMATION
*All dimensions are nominal
Device Package
Type Package
Drawing Pins SPQ Reel
Diameter
(mm)
Reel
Width
W1 (mm)
A0
(mm) B0
(mm) K0
(mm) P1
(mm) W
(mm) Pin1
Quadrant
LMH6552MAX/NOPB SOIC D 8 2500 330.0 12.4 6.5 5.4 2.0 8.0 12.0 Q1
LMH6552SD/NOPB WSON NGS 8 1000 178.0 12.4 3.3 2.8 1.0 8.0 12.0 Q1
PACKAGE MATERIALS INFORMATION
www.ti.com 5-Jan-2022
Pack Materials-Page 1
l TEXAS INSTRUMENTS TAPE AND REEL BOX DIMENSIONS
*All dimensions are nominal
Device Package Type Package Drawing Pins SPQ Length (mm) Width (mm) Height (mm)
LMH6552MAX/NOPB SOIC D 8 2500 367.0 367.0 35.0
LMH6552SD/NOPB WSON NGS 8 1000 208.0 191.0 35.0
PACKAGE MATERIALS INFORMATION
www.ti.com 5-Jan-2022
Pack Materials-Page 2
l TEXAS INSTRUMENTS T - Tube height| L - Tube length l ,g + w-Tuhe _______________ _ ______________ width 47 — B - Alignment groove width
TUBE
*All dimensions are nominal
Device Package Name Package Type Pins SPQ L (mm) W (mm) T (µm) B (mm)
LMH6552MA/NOPB D SOIC 8 95 495 8 4064 3.05
PACKAGE MATERIALS INFORMATION
www.ti.com 5-Jan-2022
Pack Materials-Page 3
* t w alt C E: C a W : vixl 3‘7“} 1 i F H x/ 3133 W, L W J
www.ti.com
PACKAGE OUTLINE
C
8X 0.3
0.2
1.5 0.1
8X 0.5
0.3
2X
1.5
1.6 0.1
6X 0.5
0.8
0.7
0.05
0.00
B3.1
2.9 A
2.6
2.4
(0.1) TYP
WSON - 0.8 mm max heightNGS0008C
PLASTIC SMALL OUTLINE - NO LEAD
4214924/A 07/2018
PIN 1 INDEX AREA
SEATING PLANE
0.08 C
1
45
8
PIN 1 ID 0.1 C A B
0.05 C
THERMAL PAD
EXPOSED
9
SYMM
SYMM
NOTES:
1. All linear dimensions are in millimeters. Any dimensions in parenthesis are for reference only. Dimensioning and tolerancing
per ASME Y14.5M.
2. This drawing is subject to change without notice.
3. The package thermal pad must be soldered to the printed circuit board for thermal and mechanical performance.
SCALE 5.000
E w @Qflflm A L Lb TL i-J PIA/H" S
www.ti.com
EXAMPLE BOARD LAYOUT
0.07 MIN
ALL AROUND
0.07 MAX
ALL AROUND
(1.6)
6X (0.5)
(2.8)
8X (0.25)
8X (0.6)
(1.5)
(R0.05) TYP
( 0.2) VIA
TYP
(0.5)
WSON - 0.8 mm max heightNGS0008C
PLASTIC SMALL OUTLINE - NO LEAD
4214924/A 07/2018
SYMM
1
45
8
SYMM
LAND PATTERN EXAMPLE
EXPOSED METAL SHOWN
SCALE:20X
9
NOTES: (continued)
4. This package is designed to be soldered to a thermal pad on the board. For more information, see Texas Instruments literature
number SLUA271 (www.ti.com/lit/slua271).
5. Vias are optional depending on application, refer to device data sheet. If any vias are implemented, refer to their locations shown
on this view. It is recommended that vias under paste be filled, plugged or tented.
SOLDER MASK
OPENING
SOLDER MASK
METAL UNDER
SOLDER MASK
DEFINED
EXPOSED METAL
METAL
SOLDER MASK
OPENING
SOLDER MASK DETAILS
NON SOLDER MASK
DEFINED
(PREFERRED)
EXPOSED METAL
www.ti.com
EXAMPLE STENCIL DESIGN
8X (0.25)
8X (0.6)
6X (0.5)
(1.38)
(1.47)
(2.8)
(R0.05) TYP
WSON - 0.8 mm max heightNGS0008C
PLASTIC SMALL OUTLINE - NO LEAD
4214924/A 07/2018
NOTES: (continued)
6. Laser cutting apertures with trapezoidal walls and rounded corners may offer better paste release. IPC-7525 may have alternate
design recommendations.
SOLDER PASTE EXAMPLE
BASED ON 0.1 mm THICK STENCIL
EXPOSED PAD 9:
82% PRINTED SOLDER COVERAGE BY AREA UNDER PACKAGE
SCALE:20X
SYMM
1
45
8
SYMM
METAL
TYP
9
‘J
www.ti.com
PACKAGE OUTLINE
C
.228-.244 TYP
[5.80-6.19]
.069 MAX
[1.75]
6X .050
[1.27]
8X .012-.020
[0.31-0.51]
2X
.150
[3.81]
.005-.010 TYP
[0.13-0.25]
0 - 8 .004-.010
[0.11-0.25]
.010
[0.25]
.016-.050
[0.41-1.27]
4X (0 -15 )
A
.189-.197
[4.81-5.00]
NOTE 3
B .150-.157
[3.81-3.98]
NOTE 4
4X (0 -15 )
(.041)
[1.04]
SOIC - 1.75 mm max heightD0008A
SMALL OUTLINE INTEGRATED CIRCUIT
4214825/C 02/2019
NOTES:
1. Linear dimensions are in inches [millimeters]. Dimensions in parenthesis are for reference only. Controlling dimensions are in inches.
Dimensioning and tolerancing per ASME Y14.5M.
2. This drawing is subject to change without notice.
3. This dimension does not include mold flash, protrusions, or gate burrs. Mold flash, protrusions, or gate burrs shall not
exceed .006 [0.15] per side.
4. This dimension does not include interlead flash.
5. Reference JEDEC registration MS-012, variation AA.
18
.010 [0.25] C A B
5
4
PIN 1 ID AREA
SEATING PLANE
.004 [0.1] C
SEE DETAIL A
DETAIL A
TYPICAL
SCALE 2.800
Yl“‘+
www.ti.com
EXAMPLE BOARD LAYOUT
.0028 MAX
[0.07]
ALL AROUND
.0028 MIN
[0.07]
ALL AROUND
(.213)
[5.4]
6X (.050 )
[1.27]
8X (.061 )
[1.55]
8X (.024)
[0.6]
(R.002 ) TYP
[0.05]
SOIC - 1.75 mm max heightD0008A
SMALL OUTLINE INTEGRATED CIRCUIT
4214825/C 02/2019
NOTES: (continued)
6. Publication IPC-7351 may have alternate designs.
7. Solder mask tolerances between and around signal pads can vary based on board fabrication site.
METAL SOLDER MASK
OPENING
NON SOLDER MASK
DEFINED
SOLDER MASK DETAILS
EXPOSED
METAL
OPENING
SOLDER MASK METAL UNDER
SOLDER MASK
SOLDER MASK
DEFINED
EXPOSED
METAL
LAND PATTERN EXAMPLE
EXPOSED METAL SHOWN
SCALE:8X
SYMM
1
45
8
SEE
DETAILS
SYMM
www.ti.com
EXAMPLE STENCIL DESIGN
8X (.061 )
[1.55]
8X (.024)
[0.6]
6X (.050 )
[1.27] (.213)
[5.4]
(R.002 ) TYP
[0.05]
SOIC - 1.75 mm max heightD0008A
SMALL OUTLINE INTEGRATED CIRCUIT
4214825/C 02/2019
NOTES: (continued)
8. Laser cutting apertures with trapezoidal walls and rounded corners may offer better paste release. IPC-7525 may have alternate
design recommendations.
9. Board assembly site may have different recommendations for stencil design.
SOLDER PASTE EXAMPLE
BASED ON .005 INCH [0.125 MM] THICK STENCIL
SCALE:8X
SYMM
SYMM
1
45
8
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