LMZ14201H Datasheet by Texas Instruments

U Ordering & Technical Design a 3 Support 5 o . quahly documentation development (raming I TEXAS INSTRUMENTS um
LMZ14201H SIMPLE SWITCHER® 6V to 42V, 1A High Output Voltage Power Module
1 Features
• Integrated shielded inductor
• Simple PCB layout
• Flexible start-up sequencing using external soft-
start and precision enable
• Protection against inrush currents
• Input UVLO and output short circuit protection
• –40°C to 125°C junction temperature range
• Single exposed pad and standard pinout for easy
mounting and manufacturing
• Low output voltage ripple
• Pin-to-pin compatible family:
– LMZ14203H/2H/1H (42 V maximum 3-A, 2-A,
1-A)
– LMZ14203/2/1 (42 V maximum 3-A, 2-A, 1-A)
– LMZ12003/2/1 (20 V maximum 3-A, 2-A, 1-A)
• Fully enabled for WEBENCH® power designer
• Electrical specifications
– Up to 1-A output current
– Input voltage range 6 V to 42 V
– Output voltage as low as 5 V
– Efficiency up to 97%
• Performance benefits
– High efficiency reduces system heat generation
– No compensation required
– Low package thermal resistance
– Low radiated EMI (EN 55022 class B tested) 1
2 Applications
•Intermediate bus conversions to 12-V and 24-V rail
•Time-critical projects
•Space constrained and high thermal requirement
applications
•Negative output voltage applications
3 Description
The LMZ14201H SIMPLE SWITCHER® power
module is an easy-to-use step-down DC-DC solution
that can drive up to 1-A load with exceptional
power conversion efficiency, line and load regulation,
and output accuracy. The LMZ14201H is available
in an innovative package that enhances thermal
performance and allows for hand or machine
soldering.
The LMZ14201H can accept an input voltage rail
between 6 V and 42 V and deliver an adjustable
and highly accurate output voltage as low as 5
V. The LMZ14201H only requires three external
resistors and four external capacitors to complete the
power solution. The LMZ14201H is a reliable and
robust design with the following protection features:
thermal shutdown, input undervoltage lockout, output
overvoltage protection, short-circuit protection, output
current limit, and allows start-up into a prebiased
output. A single resistor adjusts the switching
frequency up to 1 MHz.
Device Information
PART NUMBER(2) PACKAGE(1) BODY SIZE (NOM)
LMZ14201H TO-PMOD (7) 10.16 mm × 9.85 mm
(1) For all available packages, see the orderable addendum at
the end of the data sheet.
(2) Peak reflow temperature equals 245°C. See SNAA214 for
more details.
VIN
CIN
Enable
RON
RFBT
CFF
CSS RFBB COUT
LMZ14201H
VOUT
FB
RON
SS
VIN
EN
GND
VOUT
Simplified Application Schematic
0.0 0.2 0.4 0.6 0.8 1.0
70
75
80
85
90
95
100
EFFICIENCY (%)
OUTPUT CURRENT (A)
VIN = 15V
VIN = 24V
VIN = 30V
VIN = 36V
VIN = 42V
Efficiency VOUT = 12 V, TA = 25°C
1EN 55022:2006, +A1:2007, FCC Part 15 Subpart B: 2007.
LMZ14201H
SNVS690I – JANUARY 2011 – REVISED AUGUST 2021
An IMPORTANT NOTICE at the end of this data sheet addresses availability, warranty, changes, use in safety-critical applications,
intellectual property matters and other important disclaimers. PRODUCTION DATA.
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Table of Contents
1 Features............................................................................1
2 Applications.....................................................................1
3 Description.......................................................................1
4 Revision History.............................................................. 2
5 Pin Configuration and Functions...................................3
6 Specifications.................................................................. 4
6.1 Absolute Maximum Ratings........................................ 4
6.2 ESD Ratings............................................................... 4
6.3 Recommended Operating Conditions.........................4
6.4 Thermal Information....................................................4
6.5 Electrical Characteristics.............................................5
6.6 Typical Characteristics................................................7
7 Detailed Description......................................................15
7.1 Overview...................................................................15
7.2 Functional Block Diagram.........................................15
7.3 Feature Description...................................................15
7.4 Device Functional Modes..........................................16
8 Application and Implementation..................................17
8.1 Application Information............................................. 17
8.2 Typical Application.................................................... 17
9 Power Supply Recommendations................................22
10 Layout...........................................................................23
10.1 Layout Guidelines................................................... 23
10.2 Layout Example...................................................... 24
11 Device and Documentation Support..........................27
11.1 Documentation Support.......................................... 27
11.2 Receiving Notification of Documentation Updates.. 27
11.3 Support Resources................................................. 27
11.4 Trademarks............................................................. 27
11.5 Electrostatic Discharge Caution.............................. 27
11.6 Glossary.................................................................. 27
12 Mechanical, Packaging, and Orderable
Information.................................................................... 27
4 Revision History
NOTE: Page numbers for previous revisions may differ from page numbers in the current version.
Changes from Revision H (October 2015) to Revision I (August 2021) Page
• Updated the numbering format for tables, figures, and cross-references throughout the document. ................1
• Updated Equation 17 .......................................................................................................................................21
Changes from Revision G (August 2015) to Revision H (October 2015) Page
• Added this new bullet in the Power Module SMT Guidelines section...............................................................23
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5 Pin Configuration and Functions
Exposed Pad
Connect to GND
5 SS
6 FB
3 EN
1 VIN
2 RON
4 GND
7 VOUT
Figure 5-1. NDW Package 7-Pin TO-PMD (Top View)
Table 5-1. Pin Functions
PIN TYPE DESCRIPTION
NO. NAME
1 VIN Power Supply input — Additional external input capacitance is required between this pin and the exposed
pad (EP).
2 RON Analog ON-time resistor — An external resistor from VIN to this pin sets the ON-time and frequency of the
application. Typical values range from 100 kΩ to 700 kΩ.
3 EN Analog Enable — Input to the precision enable comparator. Rising threshold is 1.18 V.
4 GND Ground Ground — Reference point for all stated voltages. Must be externally connected to EP.
5 SS Analog Soft-Start — An internal 8 µA current source charges an external capacitor to produce the soft-start
function.
6 FB Analog Feedback — Internally connected to the regulation, overvoltage, and short-circuit comparators. The
regulation reference point is 0.8 V at this input pin. Connect the feedback resistor divider between
the output and ground to set the output voltage.
7 VOUT Power Output Voltage — Output from the internal inductor. Connect the output capacitor between this pin
and the EP.
— EP Ground Exposed Pad — Internally connected to pin 4. Used to dissipate heat from the package during
operation. Must be electrically connected to pin 4 external to the package.
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6 Specifications
6.1 Absolute Maximum Ratings
over operating free-air temperature range (unless otherwise noted)(1) (2) (3)
MIN MAX UNIT
VIN, RON to GND –0.3 43.5 V
EN, FB, SS to GND –0.3 7 V
Junction Temperature 150 °C
Peak Reflow Case Temperature
(30 sec)
245 °C
Storage Temperature –65 150 °C
(1) Stresses beyond those listed under Absolute Maximum Ratings may cause permanent damage to the device. These are stress
ratings only, which do not imply functional operation of the device at these or any other conditions beyond those indicated under
Recommended Operating Conditions. Exposure to absolute-maximum-rated conditions for extended periods may affect device
reliability.
(2) If Military/Aerospace specified devices are required, please contact the Texas Instruments Sales Office/ Distributors for availability and
specifications.
(3) For soldering specifications, refer to the following document: SNOA549
6.2 ESD Ratings
VALUE UNIT
V(ESD) Electrostatic discharge Human body model (HBM), per ANSI/ESDA/JEDEC JS-001(1) ±2000 V
(1) JEDEC document JEP155 states that 500-V HBM allows safe manufacturing with a standard ESD control process.
6.3 Recommended Operating Conditions
MIN MAX UNIT
VIN 6 42 V
EN 0 6.5 V
Operation Junction Temperature –40 125 °C
6.4 Thermal Information
THERMAL METRIC(1)
LMZ14201H
UNITNDW (TO-PMD)
7 PINS
RθJA Junction-to-ambient thermal resistance
4 layer printed-circuit-board, 7.62 cm x
7.62 cm (3 in x 3 in) area, 1 oz copper,
no air flow
16
°C/W
4 layer printed-circuit-board, 6.35 cm x
6.35 cm (2.5 in x 2.5 in) area, 1 oz
copper, no air flow
18.4
RθJC(top) Junction-to-case (top) thermal resistance 1.9 °C/W
(1) For more information about traditional and new thermal metrics, see the Semiconductor and IC Package Thermal Metrics application
report, SPRA953.
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6.5 Electrical Characteristics
Minimum and maximum limits are ensured through test, design or statistical correlation. Typical values represent the most
likely parametric norm at TJ = 25°C, and are provided for reference purposes only. Unless otherwise stated the following
conditions apply: VIN = 24 V, VOUT = 12 V, RON = 249 kΩ
PARAMETER TEST CONDITIONS MIN(1) TYP(2) MAX(1) UNIT
SYSTEM PARAMETERS
ENABLE CONTROL
VEN EN threshold trip point VEN rising, TJ = –40°C to 125°C 1.10 1.18 1.25 V
VEN-HYS EN threshold hysteresis 90 mV
SOFT-START
ISS SS source current VSS = 0 V, TJ = –40°C to 125°C 8 10 15 µA
ISS-DIS SS discharge current –200 µA
CURRENT LIMIT
ICL Current limit threshold DC average, TJ = –40°C to 125°C 1.5 1.95 2.7 A
VIN UVLO
VINUVLO Input UVLO EN pin floating
VIN rising 3.75 V
VINUVLO-HYST Hysteresis EN pin floating
VIN falling 130 mV
ON/OFF TIMER
tON-MIN ON timer minimum pulse width 150 ns
tOFF OFF timer pulse width 260 ns
REGULATION AND OVERVOLTAGE COMPARATOR
VFB In-regulation feedback voltage
VIN = 24 V, VOUT = 12 V
VSS >+ 0.8 V
TJ = –40°C to 125°C
IOUT = 10 mA to 1 A
0.782 0.803 0.822
V
VIN = 24 V, VOUT = 12 V
VSS >+ 0.8 V
TJ = 25°C
IOUT = 10 mA to 1 A
0.786 0.803 0.818
VFB In-regulation feedback voltage
VIN = 36 V, VOUT = 24 V
VSS >+ 0.8 V
TJ = –40°C to 125°C
IOUT = 10 mA to 1 A
0.780 0.803 0.823
V
VIN = 36 V, VOUT = 24 V
VSS >+ 0.8 V
TJ = 25°C
IOUT = 10 mA to 1 A
0.787 0.803 0.819
VFB-OVP Feedback overvoltage protection
threshold
0.92 V
IFB Feedback input bias current 5 nA
IQNon-Switching Input Current VFB= 0.86 V 1 mA
ISD Shut Down Quiescent Current VEN= 0 V 25 μA
THERMAL CHARACTERISTICS
TSD Thermal shutdown (rising) 165 °C
TSD-HYST Thermal shutdown hysteresis 15 °C
PERFORMANCE PARAMETERS
ΔVOUT Output Voltage Ripple VOUT = 5 V, COUT = 100 µF 6.3 V X7R 8 mVPP
ΔVOUT/ΔVIN Line Regulation VIN = 16 V to 42 V, IOUT= 1 A 0.01%
ΔVOUT/ΔIOUT Load Regulation VIN = 24 V, IOUT= 0 A to 1 A 1.5 mV/A
η Efficiency VIN = 24 V, VOUT = 12 V, IOUT = 0.5 A 94%
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Minimum and maximum limits are ensured through test, design or statistical correlation. Typical values represent the most
likely parametric norm at TJ = 25°C, and are provided for reference purposes only. Unless otherwise stated the following
conditions apply: VIN = 24 V, VOUT = 12 V, RON = 249 kΩ
PARAMETER TEST CONDITIONS MIN(1) TYP(2) MAX(1) UNIT
η Efficiency VIN = 24 V, VOUT = 12 V, IOUT = 1 A 92%
(1) Minimum and Maximum limits are 100% production tested at 25°C. Limits over the operating temperature range are ensured through
correlation using Statistical Quality Control (SQC) methods. Limits are used to calculate Average Outgoing Quality Level (AOQL).
(2) Typical numbers are at 25°C and represent the most likely parametric norm.
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6.6 Typical Characteristics
Unless otherwise specified, the following conditions apply: VIN = 24 V; Cin = 10-uF X7R Ceramic; CO = 47 uF; TA = 25°C.
0.0 0.2 0.4 0.6 0.8 1.0
70
75
80
85
90
95
100
EFFICIENCY (%)
OUTPUT CURRENT (A)
VIN = 8V
VIN = 12V
VIN = 24V
VIN = 36V
VIN = 42V
Figure 6-1. Efficiency VOUT = 5 V, TA = 25°C
0.0 0.2 0.4 0.6 0.8 1.0
0.0
0.3
0.6
0.9
1.2
1.5
POWER DISSIPATION (W)
OUTPUT CURRENT (A)
VIN = 8V
VIN = 12V
VIN = 24V
VIN = 36V
VIN = 42V
Figure 6-2. Power Dissipation VOUT = 5 V, TA = 25°C
0.0 0.2 0.4 0.6 0.8 1.0
70
75
80
85
90
95
100
EFFICIENCY (%)
OUTPUT CURRENT (A)
VIN = 15V
VIN = 24V
VIN = 30V
VIN = 36V
VIN = 42V
Figure 6-3. Efficiency VOUT = 12 V, TA = 25°C
0.0 0.2 0.4 0.6 0.8 1.0
0.0
0.3
0.6
0.9
1.2
1.5
POWER DISSIPATION (W)
OUTPUT CURRENT (A)
VIN = 15V
VIN = 24V
VIN = 30V
VIN = 36V
VIN = 42V
Figure 6-4. Power Dissipation VOUT = 12 V, TA = 25°C
0.0 0.2 0.4 0.6 0.8 1.0
70
75
80
85
90
95
100
EFFICIENCY (%)
OUTPUT CURRENT (A)
VIN = 24V
VIN = 30V
VIN = 36V
VIN = 42V
Figure 6-5. Efficiency VOUT = 15 V, TA = 25°C
0.0 0.2 0.4 0.6 0.8 1.0
0.0
0.3
0.6
0.9
1.2
1.5
POWER DISSIPATION (W)
OUTPUT CURRENT (A)
VIN = 24V
VIN = 30V
VIN = 36V
VIN = 42V
Figure 6-6. Power Dissipation VOUT = 15 V, TA = 25°C
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6.6 Typical Characteristics (continued)
Unless otherwise specified, the following conditions apply: VIN = 24 V; Cin = 10-uF X7R Ceramic; CO = 47 uF; TA = 25°C.
0.0 0.2 0.4 0.6 0.8 1.0
70
75
80
85
90
95
100
EFFICIENCY (%)
OUTPUT CURRENT (A)
VIN = 24V
VIN = 30V
VIN = 36V
VIN = 42V
Figure 6-7. Efficiency VOUT = 18 V, TA = 25°C
0.0 0.2 0.4 0.6 0.8 1.0
0.0
0.3
0.6
0.9
1.2
1.5
POWER DISSIPATION (W)
OUTPUT CURRENT (A)
VIN = 24V
VIN = 30V
VIN = 36V
VIN = 42V
Figure 6-8. Power Dissipation VOUT = 18 V, TA = 25°C
0.0 0.2 0.4 0.6 0.8 1.0
70
75
80
85
90
95
100
EFFICIENCY (%)
OUTPUT CURRENT (A)
VIN = 28V
VIN = 30V
VIN = 36V
VIN = 42V
Figure 6-9. Efficiency VOUT = 24 V, TA = 25°C
0.0 0.2 0.4 0.6 0.8 1.0
0.0
0.3
0.6
0.9
1.2
1.5
POWER DISSIPATION (W)
OUTPUT CURRENT (A)
VIN = 28V
VIN = 30V
VIN = 36V
VIN = 42V
Figure 6-10. Power Dissipation VOUT = 24 V, TA = 25°C
0.0 0.2 0.4 0.6 0.8 1.0
70
75
80
85
90
95
100
EFFICIENCY (%)
OUTPUT CURRENT (A)
VIN = 34V
VIN = 36V
VIN = 42V
Figure 6-11. Efficiency VOUT = 30 V, TA = 25°C
0.0 0.2 0.4 0.6 0.8 1.0
0.0
0.3
0.6
0.9
1.2
1.5
POWER DISSIPATION (W)
OUTPUT CURRENT (A)
VIN = 34V
VIN = 36V
VIN = 42V
Figure 6-12. Power Dissipation VOUT = 30 V, TA = 25°C
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6.6 Typical Characteristics (continued)
Unless otherwise specified, the following conditions apply: VIN = 24 V; Cin = 10-uF X7R Ceramic; CO = 47 uF; TA = 25°C.
0.0 0.2 0.4 0.6 0.8 1.0
70
75
80
85
90
95
100
EFFICIENCY (%)
OUTPUT CURRENT (A)
VIN = 8V
VIN = 12V
VIN = 24V
VIN = 36V
VIN = 42V
Figure 6-13. Efficiency VOUT = 5 V, TA = 85°C
0.0 0.2 0.4 0.6 0.8 1.0
0.0
0.3
0.6
0.9
1.2
1.5
POWER DISSIPATION (W)
OUTPUT CURRENT (A)
VIN = 8V
VIN = 12V
VIN = 24V
VIN = 36V
VIN = 42V
Figure 6-14. Power Dissipation VOUT = 5 V, TA = 85°C
0.0 0.2 0.4 0.6 0.8 1.0
70
75
80
85
90
95
100
EFFICIENCY (%)
OUTPUT CURRENT (A)
VIN = 15V
VIN = 24V
VIN = 30V
VIN = 36V
VIN = 42V
Figure 6-15. Efficiency VOUT = 12 V, TA = 85°C
0.0 0.2 0.4 0.6 0.8 1.0
0.0
0.3
0.6
0.9
1.2
1.5
POWER DISSIPATION (W)
OUTPUT CURRENT (A)
VIN = 15V
VIN = 24V
VIN = 30V
VIN = 36V
VIN = 42V
Figure 6-16. Power Dissipation VOUT = 12 V, TA = 85°C
0.0 0.2 0.4 0.6 0.8 1.0
70
75
80
85
90
95
100
EFFICIENCY (%)
OUTPUT CURRENT (A)
VIN = 24V
VIN = 30V
VIN = 36V
VIN = 42V
Figure 6-17. Efficiency VOUT = 15 V, TA = 85°C
0.0 0.2 0.4 0.6 0.8 1.0
0.0
0.3
0.6
0.9
1.2
1.5
POWER DISSIPATION (W)
OUTPUT CURRENT (A)
VIN = 24V
VIN = 30V
VIN = 36V
VIN = 42V
Figure 6-18. Power Dissipation VOUT = 15 V, TA = 85°C
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6.6 Typical Characteristics (continued)
Unless otherwise specified, the following conditions apply: VIN = 24 V; Cin = 10-uF X7R Ceramic; CO = 47 uF; TA = 25°C.
0.0 0.2 0.4 0.6 0.8 1.0
70
75
80
85
90
95
100
EFFICIENCY (%)
OUTPUT CURRENT (A)
VIN = 24V
VIN = 30V
VIN = 36V
VIN = 42V
Figure 6-19. Efficiency VOUT = 18 V, TA = 85°C
0.0 0.2 0.4 0.6 0.8 1.0
0.0
0.3
0.6
0.9
1.2
1.5
POWER DISSIPATION (W)
OUTPUT CURRENT (A)
VIN = 24V
VIN = 30V
VIN = 36V
VIN = 42V
Figure 6-20. Power Dissipation VOUT = 18 V, TA = 85°C
0.0 0.2 0.4 0.6 0.8 1.0
70
75
80
85
90
95
100
EFFICIENCY (%)
OUTPUT CURRENT (A)
VIN = 28V
VIN = 30V
VIN = 36V
VIN = 42V
Figure 6-21. Efficiency VOUT = 24 V, TA = 85°C
0.0 0.2 0.4 0.6 0.8 1.0
0.0
0.3
0.6
0.9
1.2
1.5
POWER DISSIPATION (W)
OUTPUT CURRENT (A)
VIN = 28V
VIN = 30V
VIN = 36V
VIN = 42V
Figure 6-22. Power Dissipation VOUT = 24 V, TA = 85°C
0.0 0.2 0.4 0.6 0.8 1.0
70
75
80
85
90
95
100
EFFICIENCY (%)
OUTPUT CURRENT (A)
VIN = 34V
VIN = 36V
VIN = 42V
Figure 6-23. Efficiency VOUT = 30 V, TA = 85°C
0.0 0.2 0.4 0.6 0.8 1.0
0.0
0.3
0.6
0.9
1.2
1.5
POWER DISSIPATION (W)
OUTPUT CURRENT (A)
VIN = 34V
VIN = 36V
VIN = 42V
Figure 6-24. Power Dissipation VOUT = 30 V, TA = 85°C
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MENTS \\ \ \\
6.6 Typical Characteristics (continued)
Unless otherwise specified, the following conditions apply: VIN = 24 V; Cin = 10-uF X7R Ceramic; CO = 47 uF; TA = 25°C.
-20 0 20 40 60 80 100 120 140
0.0
0.2
0.4
0.6
0.8
1.0
1.2
OUTPUT CURRENT (A)
AMBIENT TEMPERATURE (°C)
VIN = 15V
VIN = 24V
VIN = 42V
Figure 6-25. Thermal Derating VOUT = 12 V, RθJA = 16°C/W
-20 0 20 40 60 80 100 120 140
0.0
0.2
0.4
0.6
0.8
1.0
1.2
OUTPUT CURRENT (A)
AMBIENT TEMPERATURE (°C)
VIN = 15V
VIN = 24V
VIN = 42V
Figure 6-26. Thermal Derating VOUT = 12 V, RθJA = 20°C/W
-20 0 20 40 60 80 100 120 140
0.0
0.2
0.4
0.6
0.8
1.0
1.2
OUTPUT CURRENT (A)
AMBIENT TEMPERATURE (°C)
VIN = 30V
VIN = 36V
VIN = 42V
Figure 6-27. Thermal Derating VOUT = 24 V, RθJA = 16°C/W
-20 0 20 40 60 80 100 120 140
0.0
0.2
0.4
0.6
0.8
1.0
1.2
OUTPUT CURRENT (A)
AMBIENT TEMPERATURE (°C)
VIN = 30V
VIN = 36V
VIN = 42V
Figure 6-28. Thermal Derating VOUT = 24 V, RθJA = 20°C/W
-20 0 20 40 60 80 100 120 140
0.0
0.2
0.4
0.6
0.8
1.0
1.2
OUTPUT CURRENT (A)
AMBIENT TEMPERATURE (°C)
VIN = 34V
VIN = 36V
VIN = 42V
Figure 6-29. Thermal Derating VOUT = 30 V, RθJA = 16°C/W
-20 0 20 40 60 80 100 120 140
0.0
0.2
0.4
0.6
0.8
1.0
1.2
OUTPUT CURRENT (A)
AMBIENT TEMPERATURE (°C)
VIN = 34V
VIN = 36V
VIN = 42V
Figure 6-30. Thermal Derating VOUT = 30 V, RθJA = 20°C/W
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6.6 Typical Characteristics (continued)
Unless otherwise specified, the following conditions apply: VIN = 24 V; Cin = 10-uF X7R Ceramic; CO = 47 uF; TA = 25°C.
0 10 20 30 40 50 60
0
5
10
15
20
25
30
35
40
THERMAL RESISTANCE JA(°C/W)
BOARD AREA (cm2)
0LFM (0m/s) air
225LFM (1.14m/s) air
500LFM (2.54m/s) air
Evaluation Board Area
Figure 6-31. Package Thermal Resistance RθJA 4 Layer PCB
With 1-oz Copper
Figure 6-32. Line and Load Regulation TA = 25°C
Figure 6-33. Output Ripple VIN = 12 V, IOUT = 1 A, Ceramic COUT,
BW = 200 MHz
100 mV/div 1 µs/div
VOUT=12V
Figure 6-34. Output Ripple VIN = 24 V, IOUT = 1 A, Polymer
Electrolytic COUT, BW = 200 MHz
Figure 6-35. Load Transient Response VIN = 24 V VOUT = 12 V
Load Step from 10% to 100%
200 mV/Div
1 ms/Div
500 mA/Div
IOUT
VOUT=12V
Figure 6-36. Load Transient Response VIN = 24 V VOUT = 12 V
Load Step From 30% to 100%
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6.6 Typical Characteristics (continued)
Unless otherwise specified, the following conditions apply: VIN = 24 V; Cin = 10-uF X7R Ceramic; CO = 47 uF; TA = 25°C.
5 10 15 20 25 30 35 40 45
1.0
1.5
2.0
2.5
3.0
3.5
DC CURRENT LIMIT LEVEL (A)
INPUT VOLTAGE (V)
Fsw = 250kHz
Fsw = 400kHz
Fsw = 600kHz
Figure 6-37. Current Limit vs. Input Voltage VOUT = 5 V
200 300 400 500 600 700 800
0.0
0.3
0.6
0.9
1.2
1.5
1.8
POWER DISSIPATION (W)
SWITCHING FREQUENCY (kHz)
VIN = 12V
VIN = 24V
VIN = 36V
VIN = 42V
Figure 6-38. Switching Frequency vs. Power Dissipation VOUT =
5 V
5 10 15 20 25 30 35 40 45
1.0
1.5
2.0
2.5
3.0
3.5
DC CURRENT LIMIT LEVEL (A)
INPUT VOLTAGE (V)
Fsw = 250kHz
Fsw = 400kHz
Fsw = 600kHz
Figure 6-39. Current Limit vs. Input Voltage VOUT = 12 V
200 300 400 500 600 700 800
0.0
0.3
0.6
0.9
1.2
1.5
1.8
POWER DISSIPATION (W)
SWITCHING FREQUENCY (kHz)
VIN = 15V
VIN = 24V
VIN = 36V
VIN = 42V
Figure 6-40. Switching Frequency vs. Power Dissipation VOUT =
12 V
30 33 36 39 42 45
1.0
1.5
2.0
2.5
3.0
3.5
DC CURRENT LIMIT LEVEL (A)
INPUT VOLTAGE (V)
Fsw = 250kHz
Fsw = 400kHz
Fsw = 600kHz
Figure 6-41. Current Limit vs. Input Voltage VOUT = 24 V
200 300 400 500 600 700 800
0.0
0.2
0.4
0.6
0.8
1.0
1.2
1.4
1.6
1.8
POWER DISSIPATION (W)
SWITCHING FREQUENCY (kHz)
VIN = 30V
VIN = 36V
VIN = 42V
Figure 6-42. Switching Frequency vs. Power Dissipation VOUT =
24 V
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6.6 Typical Characteristics (continued)
Unless otherwise specified, the following conditions apply: VIN = 24 V; Cin = 10-uF X7R Ceramic; CO = 47 uF; TA = 25°C.
5V/Div 1 ms/Div
VOUT
ENABLE
Figure 6-43. Start-Up VIN = 24 V, IOUT = 1 A
0 200 400 600 800 1000
0
10
20
30
40
50
60
70
80
RADIATED EMISSIONS (dBV/m)
FREQUENCY (MHz)
Emissions (Evaluation Board)
EN 55022 Limit (Class B)
Figure 6-44. Radiated EMI of Evaluation Board, VOUT = 12 V
0.1 1 10 100
0
10
20
30
40
50
60
70
80
CONDUCTED EMISSIONS (dBV)
FREQUENCY (MHz)
Emissions
CISPR 22 Quasi Peak
CISPR 22 Average
Figure 6-45. Conducted EMI, VOUT = 12 V Evaluation Board BOM and 3.3-µH, 1-µF LC Line Filter
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7 Detailed Description
7.1 Overview
7.1.1 COT Control Circuit Overview
Constant ON-Time control is based on a comparator and an ON-time one-shot, with the output voltage feedback
compared to an internal 0.8V reference. If the feedback voltage is below the reference, the high-side MOSFET
is turned on for a fixed ON-time determined by a programming resistor RON. RON is connected to VIN such that
ON-time is reduced with increasing input supply voltage. Following this ON-time, the high-side MOSFET remains
off for a minimum of 260 ns. If the voltage on the feedback pin falls below the reference level again the ON-time
cycle is repeated. Regulation is achieved in this manner.
7.2 Functional Block Diagram
0.47 PF
15 PHCo
CIN
Cvcc
CBST
FB
EN
SS
Vin
Linear reg
RON
Timer
Css
RON
RFBT
RFBB
CFF
Regulator IC
VO
Internal
Passives
VOUT
GND
VIN 1
2
3
4
5
6
7
RENT
RENB
7.3 Feature Description
7.3.1 Output Overvoltage Comparator
The voltage at FB is compared to a 0.92-V internal reference. If FB rises above 0.92 V the ON-time is
immediately terminated. This condition is known as overvoltage protection (OVP). It can occur if the input voltage
is increased very suddenly or if the output load is decreased very suddenly. Once OVP is activated, the top
MOSFET ON-times will be inhibited until the condition clears. Additionally, the synchronous MOSFET will remain
on until inductor current falls to zero.
7.3.2 Current Limit
Current limit detection is carried out during the OFF-time by monitoring the current in the synchronous MOSFET.
Referring to the Section 7.2, when the top MOSFET is turned off, the inductor current flows through the load,
the PGND pin and the internal synchronous MOSFET. If this current exceeds the ICL value, the current limit
comparator disables the start of the next ON-time period. The next switching cycle will occur only if the FB input
is less than 0.8 V and the inductor current has decreased below ICL. Inductor current is monitored during the
period of time the synchronous MOSFET is conducting. So long as inductor current exceeds ICL, further ON-time
intervals for the top MOSFET will not occur. Switching frequency is lower during current limit due to the longer
OFF-time.
Note
The DC current limit varies with duty cycle, switching frequency, and temperature.
7.3.3 Thermal Protection
The junction temperature of the LMZ14201H should not be allowed to exceed its maximum ratings. Thermal
protection is implemented by an internal Thermal Shutdown circuit which activates at 165 °C (typical) causing
the device to enter a low power standby state. In this state the main MOSFET remains off causing VO to fall, and
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additionally the CSS capacitor is discharged to ground. Thermal protection helps prevent catastrophic failures for
accidental device overheating. When the junction temperature falls back below 145 °C (typical Hyst = 20 °C) the
SS pin is released, VO rises smoothly, and normal operation resumes.
7.3.4 Zero Coil Current Detection
The current of the lower (synchronous) MOSFET is monitored by a zero coil current detection circuit which
inhibits the synchronous MOSFET when its current reaches zero until the next ON-time. This circuit enables the
DCM operating mode, which improves efficiency at light loads.
7.3.5 Prebiased Start-Up
The LMZ14201H will properly start up into a prebiased output. This startup situation is common in multiple rail
logic applications where current paths may exist between different power rails during the startup sequence. The
prebias level of the output voltage must be less than the input UVLO set point. This will prevent the output
prebias from enabling the regulator through the high-side MOSFET body diode.
7.4 Device Functional Modes
7.4.1 Discontinuous Conduction and Continuous Conduction Modes
At light-load, the regulator will operate in discontinuous conduction mode (DCM). With load currents above the
critical conduction point, it will operate in continuous conduction mode (CCM). When operating in DCM the
switching cycle begins at zero amps inductor current; increases up to a peak value, and then recedes back to
zero before the end of the OFF-time. During the period of time that inductor current is zero, all load current is
supplied by the output capacitor. The next ON-time period starts when the voltage on the FB pin falls below the
internal reference. The switching frequency is lower in DCM and varies more with load current as compared to
CCM. Conversion efficiency in DCM is maintained because conduction and switching losses are reduced with
the smaller load and lower switching frequency.
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8 Application and Implementation
Note
Information in the following applications sections is not part of the TI component specification,
and TI does not warrant its accuracy or completeness. TI’s customers are responsible for
determining suitability of components for their purposes, as well as validating and testing their design
implementation to confirm system functionality.
8.1 Application Information
The LMZ14201H is a step-down DC-to-DC power module. It is typically used to convert a higher DC voltage
to a lower DC voltage with a maximum output current of 1 A. The following design procedure can be used to
select components for the LMZ14201H. Alternately, the WEBENCH software may be used to generate complete
designs.
When generating a design, the WEBENCH software utilizes iterative design procedure and accesses
comprehensive databases of components. Please go to www.ti.com for more details.
8.2 Typical Application
VIN
CIN
VIN
RON
RFBT
CFF
CSS RFBB COUT
LMZ14201H
VOUT
FB
RON
SS
VIN
EN
GND
VOUT
VOUT RFBT RFBB RON COUT COUT-ESR VIN
12V 34 k: 2.43 k: 249 k: 47 PF 1-75 m: 15 - 42V
10 PF4700 pF
0.022 PF
15V 34 k: 1.91 k: 287 k: 47 PF 1-65 m: 18 - 42V
18V 34 k: 1.58 k: 374 k: 33 PF 1-60 m: 22 - 42V
24V 34 k: 1.18 k: 499 k: 33 PF 1-60 m: 28 - 42V
30V 34 k: 931: 619 k: 33 PF 1-75 m: 34 - 42V
5V 34 k: 6.49 k: 100 k: 100 PF 1-145 m: 8 - 42V
* RENT
* RENB
* See equation 1
to calculate values
Figure 8-1. Simplified Application Schematic
8.2.1 Design Requirements
For this example the following application parameters exist.
• VIN Range = Up to 42 V
• VOUT = 5 V to 30 V
• IOUT = 1 A
Refer to the table in Figure 8-1 for more information.
8.2.2 Detailed Design Procedure
8.2.2.1 Design Steps for the LMZ14201H Application
The LMZ14201H is fully supported by WEBENCH which offers the following: component selection, electrical
simulation, thermal simulation, as well as a build-it prototype board for a reduction in design time. The following
list of steps can be used to manually design the LMZ14201H application.
1. Select minimum operating VIN with enable divider resistors.
2. Program VO with divider resistor selection.
3. Program turnon time with soft-start capacitor selection.
4. Select CO.
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5. Select CIN.
6. Set operating frequency with RON.
7. Determine module dissipation.
8. Lay out PCB for required thermal performance.
8.2.2.1.1 Enable Divider, RENT and RENB Selection
The enable input provides a precise 1.18-V reference threshold to allow direct logic drive or connection to a
voltage divider from a higher enable voltage such as VIN. The enable input also incorporates 90 mV (typical) of
hysteresis resulting in a falling threshold of 1.09 V. The maximum recommended voltage into the EN pin is 6.5
V. For applications where the midpoint of the enable divider exceeds 6.5 V, a small Zener diode can be added to
limit this voltage.
The function of the RENT and RENB divider shown in the Section 7.2 is to allow the designer to choose an input
voltage below which the circuit will be disabled. This implements the feature of programmable undervoltage
lockout. This is often used in battery-powered systems to prevent deep discharge of the system battery. It is also
useful in system designs for sequencing of output rails or to prevent early turnon of the supply as the main input
voltage rail rises at power up. Applying the enable divider to the main input rail is often done in the case of higher
input voltage systems such as 24-V AC/DC systems where a lower boundary of operation should be established.
In the case of sequencing supplies, the divider is connected to a rail that becomes active earlier in the power-up
cycle than the LMZ14201H output rail. The two resistors should be chosen based on the following ratio:
RENT / RENB = (VIN-ENABLE/ 1.18 V) – 1 (1)
The EN pin is internally pulled up to VIN and can be left floating for always-on operation. However, it is good
practice to use the enable divider and turn on the regulator when VIN is close to reaching its nominal value. This
will ensure smooth start-up and will prevent overloading the input supply.
8.2.2.1.2 Output Voltage Selection
Output voltage is determined by a divider of two resistors connected between VO and ground. The midpoint of
the divider is connected to the FB input. The voltage at FB is compared to a 0.8-V internal reference. In normal
operation an ON-time cycle is initiated when the voltage on the FB pin falls below 0.8 V. The high-side MOSFET
ON-time cycle causes the output voltage to rise and the voltage at the FB to exceed 0.8 V. As long as the
voltage at FB is above 0.8 V, ON-time cycles will not occur.
The regulated output voltage determined by the external divider resistors RFBT and RFBB is:
VO = 0.8 V × (1 + RFBT / RFBB)(2)
Rearranging terms; the ratio of the feedback resistors for a desired output voltage is:
RFBT / RFBB = (VO / 0.8 V) - 1 (3)
These resistors should be chosen from values in the range of 1 kΩ to 50 kΩ.
A feed-forward capacitor is placed in parallel with RFBT to improve load step transient response. Its value is
usually determined experimentally by load stepping between DCM and CCM conduction modes and adjusting for
best transient response and minimum output ripple.
A table of values for RFBT , RFBB , and RON is included in the simplified applications schematic.
8.2.2.1.3 Soft-Start Capacitor, CSS, Selection
Programmable soft-start permits the regulator to slowly ramp to its steady-state operating point after being
enabled, thereby reducing current inrush from the input supply and slowing the output voltage rise-time to
prevent overshoot.
Upon turnon, after all UVLO conditions have been passed, an internal 8uA current source begins charging the
external soft-start capacitor. The soft-start time duration to reach steady-state operation is given by the formula:
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tSS = VREF × CSS / Iss = 0.8 V × CSS / 8 uA (4)
This equation can be rearranged as follows:
CSS = tSS × 8 μA / 0.8 V (5)
Use of a 4700-pF capacitor results in 0.5-ms soft-start duration. This is a recommended value. Note that
high values of CSS capacitance will cause more output voltage droop when a load transient goes across the
DCM-CCM boundary. Use Equation 18 below to find the DCM-CCM boundary load current for the specific
operating condition. If a fast load transient response is desired for steps between DCM and CCM mode the
soft-start capacitor value should be less than 0.018 µF.
Note that the following conditions will reset the soft-start capacitor by discharging the SS input to ground with an
internal 200-μA current sink:
• The enable input being “pulled low”
• Thermal shutdown condition
• Overcurrent fault
• Internal VIN UVLO
8.2.2.1.4 Output Capacitor, CO, Selection
None of the required output capacitance is contained within the module. At a minimum, the output capacitor
must meet the worst-case RMS current rating of 0.5 × ILR P-P, as calculated in Equation 19. Beyond that,
additional capacitance will reduce output ripple so long as the ESR is low enough to permit it. A minimum value
of 10 μF is generally required. Experimentation will be required if attempting to operate with a minimum value.
Low-ESR capacitors, such as ceramic and polymer electrolytic capacitors are recommended.
8.2.2.1.4.1 Capacitance
Equation 6 provides a good first pass approximation of CO for load transient requirements:
CO≥ ISTEP × VFB × L × VIN/ (4 × VO × (VIN — VO) × VOUT-TRAN)(6)
As an example, for 1A load step, VIN = 24 V, VOUT = 12 V, VOUT-TRAN = 50 mV:
CO≥ 1 A × 0.8 V × 15 μH × 24 V / (4 × 12 V × ( 24 V – 12 V) × 50 mV)
CO≥ 10.05 μF
8.2.2.1.4.2 ESR
The ESR of the output capacitor affects the output voltage ripple. High ESR will result in larger VOUT peak-
to-peak ripple voltage. Furthermore, high output voltage ripple caused by excessive ESR can trigger the
overvoltage protection monitored at the FB pin. The ESR should be chosen to satisfy the maximum desired
VOUT peak-to-peak ripple voltage and to avoid overvoltage protection during normal operation. The following
equations can be used:
ESRMAX-RIPPLE ≤ VOUT-RIPPLE / ILR P-P (7)
where
• ILR P-P is calculated using Equation 19 below.
ESRMAX-OVP < (VFB-OVP - VFB) / (ILR P-P × AFB ) (8)
where
• AFB is the gain of the feedback network from VOUT to VFB at the switching frequency.
As worst-case, assume the gain of AFB with the CFF capacitor at the switching frequency is 1.
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The selected capacitor should have sufficient voltage and RMS current rating. The RMS current through the
output capacitor is:
I(COUT(RMS)) = ILR P-P / √12 (9)
8.2.2.1.5 Input Capacitor, CIN, Selection
The LMZ14201H module contains an internal 0.47 µF input ceramic capacitor. Additional input capacitance is
required external to the module to handle the input ripple current of the application. This input capacitance
should be as close as possible to the module. Input capacitor selection is generally directed to satisfy the input
ripple current requirements rather than by capacitance value.
Worst-case input ripple current rating is dictated by Equation 10:
I(CIN(RMS)) ≊ 1 / 2 × IO × √ (D / 1-D) (10)
where
• D ≊ VO / VIN
(As a point of reference, the worst-case ripple current will occur when the module is presented with full load
current and when VIN = 2 × VO).
Recommended minimum input capacitance is 10-uF X7R ceramic with a voltage rating at least 25% higher than
the maximum applied input voltage for the application. TI also recommends to pay attention to the voltage and
temperature deratings of the capacitor selected. Also note ripple current rating of ceramic capacitors may be
missing from the capacitor data sheet and you may have to contact the capacitor manufacturer for this rating.
If the system design requires a certain maximum value of input ripple voltage ΔVIN to be maintained then
Equation 11 may be used.
CIN ≥ IO × D × (1–D) / fSW-CCM × ΔVIN (11)
If ΔVIN is 1% of VIN for a 24-V input to 12-V output application this equals 240 mV and fSW = 400 kHz.
CIN≥ 1 A × 12 V/24 V × (1– 12 V/24 V) / (400000 × 0.240 V)
CIN≥ 2.6 μF
Additional bulk capacitance with higher ESR may be required to damp any resonant effects of the input
capacitance and parasitic inductance of the incoming supply lines.
8.2.2.1.6 ON-Time, RON, Resistor Selection
Many designs will begin with a desired switching frequency in mind. As seen in the Typical Characteristics
section, the best efficiency is achieved in the 300 kHz to 400 kHz switching frequency range. Equation 12 can be
used to calculate the RON value.
fSW(CCM) ≊ VO / (1.3 × 10-10 x RON)(12)
This can be rearranged as
RON ≊ VO / (1.3 × 10-10 x fSW(CCM) (13)
The selection of RON and fSW(CCM) must be confined by limitations in the ON-time and OFF-time for the COT
Control Circuit Overview section.
The ON-time of the LMZ14201H timer is determined by the resistor RON and the input voltage VIN. It is
calculated as follows:
tON = (1.3 × 10-10 × RON) / VIN (14)
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The inverse relationship of tON and VIN gives a nearly constant switching frequency as VIN is varied. RON should
be selected such that the ON-time at maximum VIN is greater than 150 ns. The ON-timer has a limiter to ensure
a minimum of 150 ns for tON. This limits the maximum operating frequency, which is governed by Equation 15:
fSW(MAX) = VO / (VIN(MAX) × 150 nsec) (15)
This equation can be used to select RON if a certain operating frequency is desired so long as the minimum
ON-time of 150 ns is observed. The limit for RON can be calculated as follows:
RON ≥ VIN(MAX) × 150 nsec / (1.3 × 10-10)(16)
If RON calculated in Equation 13 is less than the minimum value determined in Equation 16 a lower frequency
should be selected. Alternatively, VIN(MAX) can also be limited in order to keep the frequency unchanged.
Additionally, the minimum OFF-time of 260 ns (typical) limits the maximum duty ratio. Larger RON (lower FSW)
should be selected in any application requiring large duty ratio.
8.2.2.1.6.1 Discontinuous Conduction and Continuous Conduction Mode Selection
Operating frequency in DCM can be calculated as follows:
fSW(DCM) ≊ VO × (VIN-1) × 15 μH × 1.18 × 1020 × IO / ((VIN–VO) × RON 2)(17)
In CCM, current flows through the inductor through the entire switching cycle and never falls to zero during the
OFF-time. The switching frequency remains relatively constant with load current and line voltage variations. The
CCM operating frequency can be calculated using Equation 12 above.
The approximate formula for determining the DCM/CCM boundary is as follows:
IDCB ≊ VO × (VIN–VO) / ( 2 × 15 μH × fSW(CCM) × VIN)(18)
The inductor internal to the module is 15 μH. This value was chosen as a good balance between low and high
input voltage applications. The main parameter affected by the inductor is the amplitude of the inductor ripple
current (ILR). ILR can be calculated with:
ILR P-P = VO × (VIN- VO) / (15 µH × fSW × VIN)(19)
where
• VIN is the maximum input voltage and fSW is determined from Equation 12.
If the output current IO is determined by assuming that IO = IL, the higher and lower peak of ILR can be
determined. Be aware that the lower peak of ILR must be positive if CCM operation is required.
8.2.3 Application Curve
0.0 0.2 0.4 0.6 0.8 1.0
70
75
80
85
90
95
100
EFFICIENCY (%)
OUTPUT CURRENT (A)
VIN = 28V
VIN = 30V
VIN = 36V
VIN = 42V
Figure 8-2. Efficiency VOUT = 24 V, TA = 25°C
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9 Power Supply Recommendations
The LMZ14201H device is designed to operate from an input voltage supply range between 4.5 V and 42 V.
This input supply should be well regulated and able to withstand maximum input current and maintain a stable
voltage. The resistance of the input supply rail should be low enough that an input current transient does not
cause a high enough drop at the LMZ14201H supply voltage that can cause a false UVLO fault triggering and
system reset. If the input supply is more than a few inches from the LMZ14201H, additional bulk capacitance
may be required in addition to the ceramic bypass capacitors. The amount of bulk capacitance is not critical, but
a 47-μF or 100-μF electrolytic capacitor is a typical choice.
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10 Layout
10.1 Layout Guidelines
PCB layout is an important part of DC-DC converter design. Poor board layout can disrupt the performance of a
DC-DC converter and surrounding circuitry by contributing to EMI, ground bounce and resistive voltage drop in
the traces. These can send erroneous signals to the DC-DC converter resulting in poor regulation or instability.
Good layout can be implemented by following a few simple design rules.
1. Minimize area of switched current loops.
From an EMI reduction standpoint, it is imperative to minimize the high di/dt paths during PCB layout. The
high current loops that do not overlap have high di/dt content that will cause observable high frequency noise
on the output pin if the input capacitor (Cin1) is placed at a distance away from the LMZ14203. Therefore
place CIN1 as close as possible to the LMZ14203 VIN and GND exposed pad. This will minimize the high
di/dt area and reduce radiated EMI. Additionally, grounding for both the input and output capacitor should
consist of a localized top side plane that connects to the GND exposed pad (EP).
2. Have a single point ground.
The ground connections for the feedback, soft-start, and enable components should be routed to the GND
pin of the device. This prevents any switched or load currents from flowing in the analog ground traces. If
not properly handled, poor grounding can result in degraded load regulation or erratic output voltage ripple
behavior. Provide the single point ground connection from pin 4 to EP.
3. Minimize trace length to the FB pin.
Both feedback resistors, RFBT and RFBB, and the feed forward capacitor CFF, should be close to the FB pin.
Since the FB node is high impedance, maintain the copper area as small as possible. The trace are from
RFBT, RFBB, and CFF should be routed away from the body of the LMZ14203 to minimize noise.
4. Make input and output bus connections as wide as possible.
This reduces any voltage drops on the input or output of the converter and maximizes efficiency. To optimize
voltage accuracy at the load, ensure that a separate feedback voltage sense trace is made to the load.
Doing so will correct for voltage drops and provide optimum output accuracy.
5. Provide adequate device heat-sinking.
Use an array of heat-sinking vias to connect the exposed pad to the ground plane on the bottom PCB layer.
If the PCB has a plurality of copper layers, these thermal vias can also be employed to make connection to
inner layer heat-spreading ground planes. For best results use a 6 × 6 via array with minimum via diameter
of 8 mils thermal vias spaced 59 mils (1.5 mm). Ensure enough copper area is used for heat-sinking to keep
the junction temperature below 125°C.
10.1.1 Power Module SMT Guidelines
The recommendations below are for a standard module surface mount assembly
• Land Pattern – Follow the PCB land pattern with either soldermask defined or non-soldermask defined pads
• Stencil Aperture
– For the exposed die attach pad (DAP), adjust the stencil for approximately 80% coverage of the PCB land
pattern
– For all other I/O pads use a 1:1 ratio between the aperture and the land pattern recommendation
• Solder Paste – Use a standard SAC Alloy such as SAC 305, type 3 or higher
• Stencil Thickness – 0.125 mm to 0.15 mm
• Reflow - Refer to solder paste supplier recommendation and optimized per board size and density
• Refer to AN Design Summary LMZ1xxx and LMZ2xxx Power Modules Family (SNAA214) for Reflow
information
• Maximum number of reflows allowed is one
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Figure 10-1. Sample Reflow Profile
Table 10-1. Sample Reflow Profile Table
PROBE MAX TEMP
(°C)
REACHED
MAX TEMP
TIME ABOVE
235°C
REACHED
235°C
TIME ABOVE
245°C
REACHED
245°C
TIME ABOVE
260°C
REACHED
260°C
1 242.5 6.58 0.49 6.39 0 – 0 –
2 242.5 7.1 0.55 6.31 0 7.1 0 –
3 241 7.09 0.42 6.44 0 – 0 –
10.2 Layout Example
VIN
GND
VIN
VO
Cin1 CO1
Loop 1 Loop 2
LMZ14201H
VOUT
High
di/dt
Figure 10-2. Critical Current Loops to Minimize
LMZ14201H
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{5; TEXAS INSTRUMENTS "0000" .23); _r I r r, .0000, // / ‘5
RON
EN
SS
GND
FB
VIN
1 2 3 4 5 6 7
Top View
VIN
COUT
VOUT
RENT
RON
CSS
GND
Thermal Vias
VOUT
CIN
GND
RENB
CFF
RFBT
RFBB
GND Plane
EPAD
Figure 10-3. PCB Layout Guide
10.2.1 Power Dissipation and Board Thermal Requirements
For a design case of VIN = 24 V, VOUT = 12 V, IOUT = 1 A, TA (MAX) = 85°C , and TJUNCTION = 125°C, the device
must see a maximum junction-to-ambient thermal resistance of:
RθJA-MAX < (TJ-MAX – TA(MAX)) / PD(20)
This RθJA-MAX will ensure that the junction temperature of the regulator does not exceed TJ-MAX in the particular
application ambient temperature.
To calculate the required RθJA-MAX we need to get an estimate for the power losses in the IC. Figure 10-4 is
taken from the Typical Characteristics section and shows the power dissipation of the LMZ14201H for VOUT = 12
V at 85°C TA.
0.0 0.2 0.4 0.6 0.8 1.0
0.0
0.3
0.6
0.9
1.2
1.5
POWER DISSIPATION (W)
OUTPUT CURRENT (A)
VIN = 15V
VIN = 24V
VIN = 30V
VIN = 36V
VIN = 42V
Figure 10-4. Power Dissipation VOUT = 12 V, TA = 85°C
Using the 85°C TA power dissipation data as a conservative starting point, the power dissipation PD for VIN = 24
V and VOUT = 12 V is estimated to be 0.75 W. The necessary RθJA-MAX can now be calculated.
RθJA-MAX < (125°C - 85°C) / 0.75 W (21)
RθJA-MAX < 53.3°C/W (22)
To achieve this thermal resistance the PCB is required to dissipate the heat effectively. The area of the PCB
will have a direct effect on the overall junction-to-ambient thermal resistance. In order to estimate the necessary
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TEXAS INSTRUMENTS
copper area we can refer to Figure 10-5. This graph is taken from the Typical Characteristics section and shows
how the RθJA varies with the PCB area.
0 10 20 30 40 50 60
0
5
10
15
20
25
30
35
40
THERMAL RESISTANCE JA(°C/W)
BOARD AREA (cm2)
0LFM (0m/s) air
225LFM (1.14m/s) air
500LFM (2.54m/s) air
Evaluation Board Area
Figure 10-5. Package Thermal Resistance RθJA 4-Layer PCB With 1-oz Copper
For RθJA-MAX< 53.3°C/W and only natural convection (that is. no air flow), the PCB area can be smaller than
9 cm2. This corresponds to a square board with 3 cm × 3 cm (1.18 in × 1.18 in) copper area, 4 layers, and
1 oz copper thickness. Higher copper thickness will further improve the overall thermal performance. Note that
thermal vias should be placed under the IC package to easily transfer heat from the top layer of the PCB to the
inner layers and the bottom layer.
For more guidelines and insight on PCB copper area, thermal vias placement, and general thermal design
practices, refer to Application Note AN-2020 (SNVA419).
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11 Device and Documentation Support
11.1 Documentation Support
11.1.1 Related Documentation
•AN-2027 Inverting Application for the LMZ14203 SIMPLE SWITCHER Power Module, SNVA425
•Evaluation Board Application Note AN-2024, SNVA422
•AN-2026 Effect of PCB Design on Thermal Performance of SIMPLE SWITCHER Power Modules, SNVA424
•AN-2020 Thermal Design By Insight, Not Hindsight, SNVA419
•AN Design Summary LMZ1xxx and LMZ2xxx Power Modules Family, SNAA214
11.2 Receiving Notification of Documentation Updates
To receive notification of documentation updates, navigate to the device product folder on ti.com. Click on
Subscribe to updates to register and receive a weekly digest of any product information that has changed. For
change details, review the revision history included in any revised document.
11.3 Support Resources
TI E2E™ support forums are an engineer's go-to source for fast, verified answers and design help — straight
from the experts. Search existing answers or ask your own question to get the quick design help you need.
Linked content is provided "AS IS" by the respective contributors. They do not constitute TI specifications and do
not necessarily reflect TI's views; see TI's Terms of Use.
11.4 Trademarks
TI E2E™ is a trademark of Texas Instruments.
WEBENCH® and SIMPLE SWITCHER® are registered trademarks of Texas Instruments.
All trademarks are the property of their respective owners.
11.5 Electrostatic Discharge Caution
This integrated circuit can be damaged by ESD. Texas Instruments recommends that all integrated circuits be handled
with appropriate precautions. Failure to observe proper handling and installation procedures can cause damage.
ESD damage can range from subtle performance degradation to complete device failure. Precision integrated circuits may
be more susceptible to damage because very small parametric changes could cause the device not to meet its published
specifications.
11.6 Glossary
TI Glossary This glossary lists and explains terms, acronyms, and definitions.
12 Mechanical, Packaging, and Orderable Information
The following pages include mechanical, packaging, and orderable information. This information is the most
current data available for the designated devices. This data is subject to change without notice and revision of
this document. For browser-based versions of this data sheet, refer to the left-hand navigation.
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PACKAGE OPTION ADDENDUM
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Addendum-Page 1
PACKAGING INFORMATION
Orderable Device Status
(1)
Package Type Package
Drawing Pins Package
Qty Eco Plan
(2)
Lead finish/
Ball material
(6)
MSL Peak Temp
(3)
Op Temp (°C) Device Marking
(4/5)
Samples
LMZ14201HTZ/NOPB ACTIVE TO-PMOD NDW 7 250 RoHS & Green SN Level-3-245C-168 HR -40 to 125 LMZ14201
HTZ
LMZ14201HTZE/NOPB ACTIVE TO-PMOD NDW 7 45 RoHS & Green SN Level-3-245C-168 HR -40 to 125 LMZ14201
HTZ
LMZ14201HTZX/NOPB ACTIVE TO-PMOD NDW 7 500 RoHS & Green SN Level-3-245C-168 HR -40 to 125 LMZ14201
HTZ
(1) The marketing status values are defined as follows:
ACTIVE: Product device recommended for new designs.
LIFEBUY: TI has announced that the device will be discontinued, and a lifetime-buy period is in effect.
NRND: Not recommended for new designs. Device is in production to support existing customers, but TI does not recommend using this part in a new design.
PREVIEW: Device has been announced but is not in production. Samples may or may not be available.
OBSOLETE: TI has discontinued the production of the device.
(2) RoHS: TI defines "RoHS" to mean semiconductor products that are compliant with the current EU RoHS requirements for all 10 RoHS substances, including the requirement that RoHS substance
do not exceed 0.1% by weight in homogeneous materials. Where designed to be soldered at high temperatures, "RoHS" products are suitable for use in specified lead-free processes. TI may
reference these types of products as "Pb-Free".
RoHS Exempt: TI defines "RoHS Exempt" to mean products that contain lead but are compliant with EU RoHS pursuant to a specific EU RoHS exemption.
Green: TI defines "Green" to mean the content of Chlorine (Cl) and Bromine (Br) based flame retardants meet JS709B low halogen requirements of <=1000ppm threshold. Antimony trioxide based
flame retardants must also meet the <=1000ppm threshold requirement.
(3) MSL, Peak Temp. - The Moisture Sensitivity Level rating according to the JEDEC industry standard classifications, and peak solder temperature.
(4) There may be additional marking, which relates to the logo, the lot trace code information, or the environmental category on the device.
(5) Multiple Device Markings will be inside parentheses. Only one Device Marking contained in parentheses and separated by a "~" will appear on a device. If a line is indented then it is a continuation
of the previous line and the two combined represent the entire Device Marking for that device.
(6) Lead finish/Ball material - Orderable Devices may have multiple material finish options. Finish options are separated by a vertical ruled line. Lead finish/Ball material values may wrap to two
lines if the finish value exceeds the maximum column width.
Important Information and Disclaimer:The information provided on this page represents TI's knowledge and belief as of the date that it is provided. TI bases its knowledge and belief on information
provided by third parties, and makes no representation or warranty as to the accuracy of such information. Efforts are underway to better integrate information from third parties. TI has taken and
continues to take reasonable steps to provide representative and accurate information but may not have conducted destructive testing or chemical analysis on incoming materials and chemicals.
TI and TI suppliers consider certain information to be proprietary, and thus CAS numbers and other limited information may not be available for release.
I TEXAS INSTRUMENTS
PACKAGE OPTION ADDENDUM
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Addendum-Page 2
In no event shall TI's liability arising out of such information exceed the total purchase price of the TI part(s) at issue in this document sold by TI to Customer on an annual basis.
l TEXAS INSTRUMENTS REEL DIMENSIONS TAPE DIMENSIONS 7 “K0 '«m» Reel Diame|er AD Dimension deswgned to accommodate the componem wwdlh E0 Dimension desxgned to accommodate the componenl \ength KO Dimenslun deswgned to accommodate the componem thickness 7 w OveraH wwdm loe earner cape i p1 Pitch between successwe cavuy cemers f T Reel Width (W1) QUADRANT ASSIGNMENTS FOR PIN 1 ORIENTATION IN TAPE O O O D O O D O Sprockemoles ,,,,,,,,,,, ‘ User Direcllon 0' Feed Pockel Quadrams
TAPE AND REEL INFORMATION
*All dimensions are nominal
Device Package
Type Package
Drawing Pins SPQ Reel
Diameter
(mm)
Reel
Width
W1 (mm)
A0
(mm) B0
(mm) K0
(mm) P1
(mm) W
(mm) Pin1
Quadrant
LMZ14201HTZ/NOPB TO-
PMOD NDW 7 250 330.0 24.4 10.6 14.22 5.0 16.0 24.0 Q2
LMZ14201HTZX/NOPB TO-
PMOD NDW 7 500 330.0 24.4 10.6 14.22 5.0 16.0 24.0 Q2
PACKAGE MATERIALS INFORMATION
www.ti.com 4-Jan-2022
Pack Materials-Page 1
l TEXAS INSTRUMENTS TAPE AND REEL BOX DIMENSIONS
*All dimensions are nominal
Device Package Type Package Drawing Pins SPQ Length (mm) Width (mm) Height (mm)
LMZ14201HTZ/NOPB TO-PMOD NDW 7 250 367.0 367.0 45.0
LMZ14201HTZX/NOPB TO-PMOD NDW 7 500 367.0 367.0 45.0
PACKAGE MATERIALS INFORMATION
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Pack Materials-Page 2
l TEXAS INSTRUMENTS T - Tube height| L - Tube length l ,g + w-Tuhe _______________ _ ______________ width 47 — B - Alignment groove width
TUBE
*All dimensions are nominal
Device Package Name Package Type Pins SPQ L (mm) W (mm) T (µm) B (mm)
LMZ14201HTZE/NOPB NDW TO-PMOD 7 45 502 17 6700 8.4
PACKAGE MATERIALS INFORMATION
www.ti.com 4-Jan-2022
Pack Materials-Page 3
r A pm +m munu m, ,A, van uw u, w my / I” M H ‘ ‘ ‘IL F—-—4 r = r. ‘ \ le>iwsrm w 1 DwiusloNs m IN mum»: \ / ‘ ‘x’ ,4 g ‘ 4w M u“ 13W (Wm m mm m A TEXAS INSTRUMENTS
MECHANICAL DATA
NDW0007A
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TOP SIDE OF PACKAGE
BOTTOM SIDE OF PACKAGE
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